|USFDC Home | USF Electronic Theses and Dissertations||| RSS|
This item is only available as the following downloads:
xml version 1.0 encoding UTF-8 standalone no
record xmlns http:www.loc.govMARC21slim
leader nam 22 Ka 4500
controlfield tag 007 cr-bnu---uuuuu
008 s2010 flu s 000 0 eng d
datafield ind1 8 ind2 024
subfield code a E14-SFE0004728
A microwave radiometer for close proximity core body temperature monitoring :
b design, development and experimentation
h [electronic resource] /
by Quenton Bonds.
[Tampa, Fla] :
University of South Florida,
Title from PDF of title page.
Document formatted into pages; contains X pages.
Dissertation (PHD)--University of South Florida, 2010.
Includes bibliographical references.
Text (Electronic thesis) in PDF format.
Mode of access: World Wide Web.
System requirements: World Wide Web browser and PDF reader.
ABSTRACT: Presented is a radiometric sensor and associated electromagnetic propagation models, developed to facilitate non-invasive core body temperature extraction. The system has been designed as a close-proximity sensor to detect thermal emissions radiated from deep-seated tissue 1 cm 3 cm inside the human body. The sensor is intended for close proximity health monitoring applications, with potential implications for deployment into the improved astronaut liquid cooling garment (LCG). The sensor is developed for high accuracy and resolution. Therefore, certain design issues that distort the close proximity measurement have been identified and resolved. An integrated cavity-backed slot antenna (CBSA) is designed to account for antenna performance degradation, which occurs in the near field of the human body. A mathematical Non-Contact Model (NCM) is subsequently used to correlate the observed brightness temperature to the subsurface temperature, while accounting for artifacts induced by the sensor's remote positioning from the specimen. In addition a tissue propagation model (TPM) is derived to model incoherent propagation of thermal emissions through the human body, and accounts for dielectric mismatch and losses throughout the intervening tissue layers. The measurement test bed is comprised of layered phantoms configured to mimic the electromagnetic characteristics of a human stomach volume; hence defines the human core model (HCM). A drop in core body temperature is simulated via the HCM, as the sensor monitors the brightness temperature at an offset distance of approximately 7 mm. The data is processes through the NCM and TPM; yielding percent error values < 3%. This study demonstrates that radiometric sensors are indeed capable of subsurface tissue monitoring from the near field of the body. However, the following components are vital to achieving an accurate measurement, and are addressed in this work: 1) the antenna must be designed for optimum functionality in close proximity to biological media; 2) a multilayer phantom model is needed to accurately emulate the point of clinical diagnosis across the tissue depth; 3) certain parameters of the non-contact measurement must be known to a high degree of accuracy; and 4) a tissue propagation model is necessary to account for electromagnetic propagation effects through the stratified tissue.
Advisor: Thomas Weller, Ph.D.
Near-Field Antenna Design
Electromagnetic Propagation and Modeling of the Human Body
Radio Frequency Tissue Phantom Development
x Electrical Engineering
t USF Electronic Theses and Dissertations.
A Microwave Radiometer for Close Proximity Core Body Temperature Monitoring: Design, Development, and Experimentation by Quenton Bonds A dissertation submitted in partial fulfillment of the requirements for the degree of Doctor of Philosophy Department of Electrical Engineering College of Engineering University of South Florida Major Professor: Thomas Weller, Ph.D. Venkat Bhethanabotla, Ph.D. Kenneth Buckle, Ph.D. Andre w Hoff, Ph.D. Ashanti Johnson Ph.D. Date of Approval: September 24, 2010 Keywords: Non Invasive Sensing Near Field Radiometry Near Field Antenna Design Electromagnetic Propagation and Modeling of the Human Body, Radio Frequency Tissue Phantom Development Copyright 2010, Quenton Bonds
DEDICATION To the young man or woman who is unaware of the unimaginable possibilities, and exciting opportunities that exist in the fields of science, technology, engineering and mathematics (STEM). To my former students of The Calhoun School and Project Success Alternative Learning Center in Lowndes County Alabama. To Telender Edwards, whose letter inspired me to push on when: 1) I was unmotivated; 2) I was extr emely tired in the we e hours of the morning but still had work to do; and 3) at times I would ask myself, Why am I doing this?', as I fought through the pain of the process, and my very purpose for pursuing the PhD was brought into question. To the youth of the slums, barrios and ghettos around the world, and last but not least, to the students of the Accelerat ed Destiny Technology Institute: this dissertation is dedicated to you!
ACKNOWLEDGEMENTS I would like to first thank the many organizations and fellowship programs that supported me throughout this process such as the FEF and McKnight, the NSF sponsored Bridge to Doctorate Program (BD), IEEE, UNCF SP, and especially the NASA sponsored Harriet Jenkins and GSRP programs. Thanks t o my church family at Without Walls International Church and Trin ity Life Center for always believing in me Moreover, I offer special thanks to my advisor, Dr. Thomas Weller. In addition to the technical skills and knowledge you have imparted into me du ring my tenure at USF, I have also become a better leader and husband as a result of watching and weaning from you over the past six years. Thanks to Dr. John Gerig for his assistance on the project and design of the 2 nd generation sensor. To all of my E NB 412 colleagues, thanks for keeping things interesting To Bernard Batson for making sure I was well taken care of, many years after my matriculation through the BD p rogram. To my family, and mother especially, Ms. Debra Bonds, thank you for expecting n othing less than greatness out of me. To my mentor, Dr. Eric Maxwell whose wisdom, guidance and spiritual insight have been essential to my successes in the PhD program To Anthony Spita l ie ri, and Brian Norris, thanks for making me realize that I am a wor ld changer. And last but not least to my beautiful wife, how do I articulate how much of a help you 've been during the se final and most critical months of this dissertation process? The meals were phenomenal, your wisdom priceless, and your love indescri bable. I love you Terinee Jade Bonds!
i TABLE OF CONTENTS LIST OF TABLES ................................ ................................ ................................ ............. iii LIST OF FIGURES ................................ ................................ ................................ ........... iv ABSTRACT ................................ ................................ ................................ ...................... vii CHAPTER 1 !! INTRODUCTION ................................ ................................ ....................... 1 1.1 Motivation ................................ ................................ ................................ ......... 2 1.2 Contributions to the Practice ................................ ................................ ............. 4 1.3 Organization of the Dissertation ................................ ................................ ....... 6 CHAPTER 2 !! A REVIEW OF MICROWAV E RADIOMETRY ................................ ..... 8 2.1 Theory ................................ ................................ ................................ ............... 8 2.2 Biomedical Radiometric S ensing ................................ ................................ .... 10 2.3 Contact Radiometry ................................ ................................ ........................ 12 2.3.1 !! A Radiometric Sensor for Blood Glucose Monitoring .................... 12 2.3. 1.1 !! Design and Specifications ................................ ................. 12 188.8.131.52 !! Measurement and Results ................................ ................. 13 2.3.2 !! RTM 01 RES ................................ ................................ ................... 14 184.108.40.206 !! Design and Spe cifications ................................ ................. 15 220.127.116.11 !! Measurement and Results ................................ ................. 16 2.4 Limitations of the Contact Radiometry ................................ ........................... 18 2.5 Non Contact Radiometric Sensing ................................ ................................ 20 CHAPTER 3 !! PRELIMINARY STUDY: T HE 1 ST GENERATION DESIGN ............... 22 3.1 A TPR Designed for Biomedical Sensing Applications ................................ 24 3.2 Calibration ................................ ................................ ................................ ....... 26 3.3 Antenna Requirements for Biomedical Radiometric Sensing ........................ 28 3.4 The Printed Dipole Antenna (PD1) ................................ ................................ 29 3.4.1 !! Characterization ................................ ................................ ............... 3 0 3.4.2 !! Body Effects ................................ ................................ ..................... 33 3.4.3 !! Cavity Effects ................................ ................................ ................... 34 3.5 Measurement Test Bed ................................ ................................ ................... 36 3.5.1 !! Blood Fatty Tissue P hantom ................................ ............................ 37 3.5.2 !! Hybrid Skin Muscle Phantom ................................ .......................... 40 3.6 Measurement Results ................................ ................................ ...................... 43 3.7 Conclusion ................................ ................................ ................................ ...... 46
ii CHAPTER 4 !! 2 ND GENERATION DESIG N ................................ ................................ ... 47 4.1 Design of a Microwave Radiometer for Biomedical Sensing (MRBS) ........... 47 4.2 Calibration ................................ ................................ ................................ ....... 50 4.3 !! A Cavity Backed Slot Antenn a (CBSA) for Near Field Biomedical ................. Radiometry ................................ ................................ ................................ ...... 51 4.3.1 !! CBSA Design Concept ................................ ................................ ..... 52 4.3.2 !! Simulations ................................ ................................ ....................... 53 4.3.3 !! Measurements and Human Body Characterization .......................... 55 4.4 Measurement Test Bed ................................ ................................ ................... 59 4.4.1 !! Rationale for the Human Core Model ................................ .............. 60 4.4.2 !! Design of the Human Core Model ................................ ................... 61 4.5 Experimentation ................................ ................................ .............................. 62 4.6 Con clusion ................................ ................................ ................................ ...... 64 CHAPTER 5 THE NON CONTACT MODE L ................................ .............................. 66 5.1 Derivation ................................ ................................ ................................ ....... 67 5.1.1 !! Stage 1 Measurement of the Brightness Temperature .................. 68 5.1.2 !! Stage 2 Correction at the Antenna Interface ................................ 68 5.1.3 !! Stage 3 Correction at the Air TUI Interface ................................ 72 5.2 Implementation ................................ ................................ ............................... 73 5.2.1 !! Data and Results ................................ ................................ ............... 73 5.2.2 !! Sensitivity Analysis of the NCM Parameters ................................ .. 76 5.3 Conclusion ................................ ................................ ................................ ...... 81 CHAPTER 6 TISSUE PROPAGATION M ODEL (TPM) ................................ ............. 83 6.1 Rationale for the TPM ................................ ................................ .................... 83 6.2 The TPM Derivation ................................ ................................ ....................... 85 6.2.1 !! Definition of the Individual Strata Emissions ................................ .. 87 6.2.2 !! Derivation of the Up and Down Welling Emissions per Layer ....... 88 6.2.3 !! Derivation of the Net Appare nt Emissions from all Stratum ........... 89 6.2.4 !! Derivation of Apparent Brightness Emissions ................................ 90 6.3 Applying the TPM ................................ ................................ .......................... 91 6.4 Core Body Temperature Extraction ................................ ................................ 92 6.5 Conclusion ................................ ................................ ................................ ...... 93 CHAPTER 7 SUMMARY AND RECOMMEN DATIONS FOR FUTURE WORKS ................................ ................................ ................................ ..... 94 7.1 Summary ................................ ................................ ................................ ......... 94 7.2 Recommendations for Future Works ................................ .............................. 99 LIST OF REFERENCES ................................ ................................ ................................ 102 !
iii LIST OF TABLES Table 1. Theoretical design specification of Ballew's radiometer. ................................ .. 13 Table 2. RTM 01 RES device specifica t i ons ................................ ................................ 15 Table 3. Dimensions of PD1. ................................ ................................ ........................... 31 Table 4. PD1 a ntenna characteristics ................................ ................................ .............. 33 Table 5. Dimensions of PD and PD RE ................................ ................................ ............. 36 Table 6. Recipe for blood fatty tissue phantom [24 ] ................................ ...................... 38 Table 7. Recipe for hybrid skin muscle phantom. ................................ ........................... 41 Table 8. PD1 versus CBSA performance characteristics. ................................ ................ 65 Table 9. Calculated values of t Z t t and L t ................................ ................................ 91
iv LIST OF FIGURES Figure 1. Surface body temperature (left) versus core temperature (right). ...................... 4 Figure 2. Comparison of Rayleigh Jean's law and Planck's law at normal body temperature 98 F. ................................ ................................ ............................ 10 Figure 3. The radiometer output monitored as blood glucose level changes. .................. 14 Figure 4. Thermal distribution of a healthy (left) and cancerous (right) breast. .............. 17 Figure 5. Thermogram of a deformed (red dashed) and healthy spine (blue). .............. 18 Figure 6. Radiometric sen sor positioned in the near field of a human core model (HCM). ................................ ................................ ................................ .............. 21 Figure 7. Block diagram of the TPR. ................................ ................................ ............... 26 Figure 8. Calibration curves of the TPR. ................................ ................................ ......... 28 Figure 9. Momentum simulation of PD1. ................................ ................................ ........ 30 Figure 10. Front (left), side (middle), and back (right) views of PD1. ............................ 31 Figure 11. Measured versus simulated S11 of the printed dipole antenna in free space. ................................ ................................ ................................ ............... 32 Figure 12. Measured versus simulated normalized radiation pattern of PD1 in dB scale. ................................ ................................ ................................ ................ 32 Figure 13. Antenna S11 degradation versus offset distance from the phantom . ........... 34 Figure 14. Non metal cavity used for the printed dipole antenna ................................ ... 35 Figure 15. Bottom (lef t) and top (right) views of the PD1 inside the cavity. .................. 35 Figure 16. Cavity effects of PD1 versus PD RE ................................ ................................ 36 Figure 17. Development process for th e blood fatty tissue phantom. ............................. 38
v Figure 18. Comparison of the real ( # r ) and imaginary ( # '' r ) dielectric constant ( # r ) of the blood fatty tissue phantom to the Gabriel model. ................................ 39 Figure 19. Comparison of the blood fatty tissue phantom impedance (Z) to the Gabriel model. ................................ ................................ ................................ 39 Figure 20. The hybrid skin muscle phantom ................................ ................................ .. 41 Figure 21 Development process for the hybrid skin muscle phantom. .......................... 41 Figure 22. Comparison of the real ( # r ) and imaginary ( # '' r ) dielectric constant ( # r ) of the skin phantom to the Gabriel model ................................ ...................... 42 Figure 23. Comparison of the skin phantom impedance (Z) to the Gabriel m odel ........ 42 Figure 24. Comparison of the real ( # r ) and imaginary ( # '' r ) dielectric constant ( # r ) of the muscle phantom to the Gabriel model. ................................ ................. 43 Figure 25. Comparison of the muscle phantom impedance (Z) to the Gabriel model. .... 43 Figure 26. 1 st g eneration m easurement test bed. ................................ .............................. 45 Figure 27. Results normalized phantom measurements: TPR vs i nfrared thermometer (surface) and digital t hermometer (internal). ............................. 45 Figure 28. Block diagram of the MRBS. ................................ ................................ ......... 50 Figure 29. Dimensions of the CBSA. ................................ ................................ .............. 53 Figure 30. CBSA design parameters and their effect on bandwidth (BW) and design frequency ( f c ). ................................ ................................ ................................ 54 Figure 31. Simulations if S11 in close proximity to a muscle tissue pha ntom. ............... 55 Figure 32. S11: measured versus simulated results with the phantom offset 7 mm from the CBSA. ................................ ................................ .............................. 56 Figure 33. Measured versus simulated normalized radiation pattern of CBSA in dB scale. ................................ ................................ ................................ ................ 57 Figure 34. S11 in free space versus phantom with 7 mm offset. ................................ ..... 58 Figure 35. S11: human core versus phantom with 7 mm offset. ................................ ..... 59 Figure 36. The human core model (HCM). ................................ ................................ ..... 62
vi Figure 37 2 nd g eneration m easurement test bed. ................................ ............................ 64 Figu re 38. Stages of the NCM. ................................ ................................ ........................ 68 Figure 39. Antenna near field main primary probing footprint (90 " # 270) and secondary probing hemisphere (90 < < 270) in the elevation (" ) plane. ................................ ................................ ................................ ............... 71 Figure 40. Corrections at the antenna interface. ................................ .............................. 71 Figure 41. Physically measured temperatures of skin and core model (dashed lines) and brightness temperature measurements (solid lines) before (T'' SKN ) and after applying the NCM (T' SKN T SKN ). ................................ .................... 75 Figure 42. Absolute, percent difference between the core temperature (Nom), skin surface (Skin) and radiometer measurements before (T'' SKN ) and after (T' SKN T SKN ) applying the NCM. ................................ ................................ ... 75 Figure 43. Percent error in the T SKN measurement taken at 15 minute intervals as X is varied from the nominal value (Nom) of 0.957 ................................ ..... 77 Figure 44. 12 Percent error in the T SKN measurement taken at 15 minute intervals as T DN is varied from the nominal value (Nom) of 65 F. ................................ 78 Figure 45. Percent error in the T SKN measurement taken at 15 minute intervals as T SL is varied from the nominal value (Nom) of 65 F. ................................ .. 79 Figure 46. Percent error in the T SKN measurement taken at 15 minute intervals as $ P is varied from the nominal value (Nom) of 65 K. ................................ ... 80 Figure 47. Percent error in the T SKN measurement taken at 15 minute intervals as e is varied from the nominal value (Nom) of 0.444. ................................ ...... 80 Figure 48. Percent error in the T SKN measurement taken at 15 minute intervals as % e is varied from the nominal value (Nom) of 0.88. ................................ .... 81 Figure 49. Graphical representation of the TPM. ................................ ............................ 87 Figure 50. Emitted brightne ss temperature at the surface (S kin) of the HCP measured by the MRBS and compared to the TPM and Wilheit model. ....... 92 Figure 51 Percent error plots: MRBS TPM, MRBS Wilheit, Model and Wilheit TPM . ................................ ................................ ................................ ........... 92
vii ABSTRACT Presented is a radiometric sensor and associated electromagnetic propagation models, developed to facilitate non invasive core body temperature extraction. The system has been designed as a close proximity sensor to detect therma l emissions radiated from deep seated tissue 1 cm 3 cm inside the human body. The sensor is in tended for close proximit y h ealth monitoring applications, with potential implications for deployment into the improved astronaut liquid cooling garment (LCG). The sensor is developed for high accuracy and resolution. Therefore, c ertain design issues that distort the close proxi mity measurement have been identified and resolved. An integrated cavity backed slot a ntenna (CBSA ) is designed to account for antenna performance degradation, which occurs in the near field of the human body A m athematical Non Contact Model (NCM) is subsequently used to correlate the observed brightness temperature to the subsurface temperature, while accounting for artifacts induced by the sensor's remote positioning from the specimen. In addition a tissue propagation model (TPM) is derived to model incoherent propagation of thermal emissions through the human body, and accounts for dielectric mismatch and losses throughout the intervening tissue layers The measurement test bed is comprised of l ayered phantoms configured to mimic the electromagneti c characteri stics of a human stomach volume; hence defines the human core model (HCM) A drop in core body temperature is simulated via the HCM, as the
viii sensor monitors the brightness temperature at an offset distance of approximately 7 mm. The data is pro cesses through the NCM and TPM ; yielding percent error values < 3%. T his study demonstrate s that radiometric sensors are indeed capable of subsurface tissue monitoring from the near field of the body. However, t he following components are vital to achiev ing an accurate measurement and are addressed in this work : 1) the antenna must be designed for optimum functionality in close proximity to biological media; 2) a multilayer phantom model is needed to accurately emulate the point of clinical diagnosis acr oss the tissue depth; 3) certain parameters of the non contact measurement must be known to a high degree of accuracy; and 4) a tissue propagation model is necessary to account for electromagnetic propagation effects through the stratified tissue.
1 CHAPTER 1 INTRODUCTION Microwave radiometers have been used in a wide range of remote sensing applications such as astronomy, atmospheric science and geology ; however in the past 35 years they have also been studied for use in the area of biomedical microwave sensing. Biomedical microwave sensing is the science of using Radio Frequency (RF) devices and instrumentation as a way of retrieving biological data from the human body. Microwave senso rs can nondestructively meas ure and or quantify certain properties of objects in harsh or sensitive environments where direct contact to the object under investigation is unachievable  One suc h environment is the human body, where in the objects under investigation are internal tissue and organs. Advances in microwave radiometry have facilitated the use of RF technology in biomedical sensing applications by retrieving the electrical and thermal properties of human tissue and organs. As a result microw ave radiometers have been used in cancer (brain, breast, thyroid, etc) detection/treatment, hyperthermia, and biomedical imaging by means of microwave thermography   As microwave radiometry becomes more prevalent in biomedical applications, this work explores the feasibility of a close proximity modality for non invasive monit oring of human tissue. The aim of this work is research and development towards subsurface monitoring of absolute tissue temperatures from the near field of the human body. In an effort to diagnose core body temperature, w e are particularly interested in
2 noninvasively measuring the thermal emissions radiated from blood fatty tissue through layers of skin and muscle RF tissue phantoms are implemented as the measurement test bed to simulate the human body in normal and adverse conditions. The sensor is intended to be deployed inside the uniforms of servicemen or as a hand held device for non contact monitoring of temperature differentials inside the human body. Therefore the radiom eter and measurement test bed were configured to replicate a health sensor positioned a short distances (10 mm 50 mm ) from the body. The goal is to identify, analyze, and mitigate the problems associated with close proximity, non invasive health monitoring using radiometric sensors Previous studies have shown that developing an application specific (human monitoring) sensor a nd anenna design are essential to achieving such goals in the on body approach   Based on our preliminary work s, we have discovered that modeling of the propagation effects in the tissue and antenna body near field is also vital, especially f or the non contact measurement. Therefore the antenna, mea surement test bed and associated propagation models developed for this work are the main contributions of this study. 1.1 Motivation The current sensor is intended for integration into the astronaut Liquid Cooling Garment (LCG) to non invasively monitor a stronaut core temperature in the improved lunar extravehicular activity (EVA) suit. Transition from extreme environments during lunar missions could lead to large differences in skin surface temperature and core body temperature ( Figure 1 ). To achieve thermal stabilization heat is discarded from the liquid cooling system through a network of tubes. Physiological studies have proven that skin
3 surface temperature alone does not provide an accurate estimate of core body temperature even with correction  Therefore the inlet temperature of the EVA suit does not alone provide sufficient diagnostic data. As a result, sensors that measure the skin surface temperature and or inlet suit temperature such as thermistors, infrared IR thermometers, or thermocouples, should be supplemented with additional measurement modalities which are capable of subsurface data extraction. Microwave radiometry serves as a feasible solution since radiometric sensors detect e lectromagnetic radiation naturally emitted across the depth of the tissue/material under investigation (T/MUI) in the form of brightness temperature. By means of microwave thermography, the detected brightness temperature is used to generate thermal gradie nts of TUI. Hence, our prime focus is to noninvasively monitor human core temperature and variations thereof by analyzing the brightness temperature data extracted from the measurement. The current sensor is designed to operate within the L frequency band of 1 GHz 2 GHz a spectrum which permits sufficient detection of emissions from deep within the body. The theoretical detection depth is up to 30 mm, enabling thermographic measurements through layers of skin fat and muscle tissue  ; as a result the extraction of core body temperature is possible with proper positi o n in g T he long term goal for this work is to expand the utility of the system to a network of radiometric sensors positioned throughout the uniform of astr onauts or servicemen at clinical diagnostic points (i.e. wrist pulse, chest heart beat, and core body temperature) for retrieving various physiological data from the body.
4 Figure 1 S urface body temperature (left) versus core temperature (right) 1.2 Contributions to the Practice This study is expected to be the trailblazer for future works in area of clo se proximity biomedical sensing and health monitoring using microwave radiometers S ubsequent contributions to the advancement of the practice have been made in the areas of antenna sensor design for biomedical applications, RF tissue phantom development, electromagnetic propagation effects in the near field of the body and electromagnetic propagation through out stratified tissue C lose proximity tracking of tissue temperature i s conceptually demonstrated in the preliminary study of a total power radiometer (TPR) which is the 1 st generation design This initial study demonstrates the sensor design consider ations from a biomedical sensing perspective In particular, the effects of calibration, thermal stabilization, antenna front end integration, and the de sign of the antenna itself, has a substantial effect on the accuracy of the measurement The se desi gn considerations are employed in the development of the 2 nd generation sensor which incorporates various design enhancements that improve the performance of the sensor Measurement and testing is performed on RF tissue phantoms which have been designed to mimic the electrical properties of human skin, muscle, and blood fatty tissue in the L frequency band A notable contribution in this area is the development of a solid Core Body Temperature Surface Body Temperature
5 skin muscle phantom in composite form. Layered configurations of these phantoms a re used to develop the human core model (HCM), which is believed to be the first phantom model configured to mimic a three dimensional volume of an abdominal cavity. S ome of the most significant contributions of this work are in the areas of antennas and propagation as the antenna design has been deemed "critical" to the radiometric measurement For this reason, we have identified t he antenna requirements for bi omedical radiometric sens ing applications. We have also demonstrated certain near field prop agation effects which distort the performance of the antenna at short distances from the body. An analysis of these near field effects is used to design a cavity backed slot antenna (CBSA), with characteristics that circumvent these phenomena enabling op timal sensor performance in the presence of human tissue The CBSA has also been designed to meet the necessary requirements for microwave biomedical sensing In the context of electromagnetic propagation, there are certain artifacts that obstruct the c lose proximity measurement that cannot be accounted for in the antenna design. Thes e artifacts are identified and a mathematical formulation in the form of a n on contact propagation model is derived to compensate for them A sensitivity analysis is performed to determine the non contact parameters to which the measurement is most sensitive. A tissue propagation model (TPM) is developed to emulate the electromagnetic propagation effects, taking into account losses and diele ctric mismatch as thermal emissions propagate through the body The TPM presented and applied to the human core model (HCM) a physical representation of a conical stomach volume of skin, muscle, and blood fatty tissue. T he brightness temperature measure ments for the HCM
6 extracted by the radiometer are correlated to the TPM. This provides an expression for the emitted temperature at the skin surface as a function of the emissions from the intervening layers Ultimately the core temperature can be reso lved b y solving for the muscle temperature in the TPM radiometer expression by applying heat transfer theory to the thermal profile of the tissue 1.3 Organization of the Dissertation This dissertation is organized into six chapters. Chapter 2 presents an overview of microwave radiometry theory a review radiometric sensors design for biomedical applications and justification for the close proximity Chapter 3 presents a preliminary investigation of the 1 st generation TPR to establish a benchmark measurement for comparison purposes throughout the remainder of the work In this chapter various tissue phantoms have been identified and characterized for testing purposes. A n analysis of the antenna performance characteristi cs in the antenna body near field is used to identify occurrences which impede the measurement. As a result, certain design methods have been implemented to compensate for these near field effects. Ultimately, p roof of concept is established in this chap ter through successful tracking of a blood fatty tissue phantom within the dynamic range of human body temperatures. Chapter 4 presents the 2 nd generation design which incorporates enhancements to the sensor, antenna, and measurement test bed. Enhance ments to the sensor include continuous calibration and miniaturization for improved perfo r mance The antenna a cavity backed slot antenna, is designed to preserve functionality in the presence of human
7 tissue. The measurement test bed is enhanced to a m ultilayer human core model (HCM) which mimics the electrical properties of an abdominal cavity across the depth of the tissue The experimental setup is also presented in this chapter. Chapter 5 presents the derivation of the non contact model (NCM) which accounts for obstructive artifacts which further impede the close proximity measurement. A considerable improvement in accuracy is achieved after the experimental data from Chapter 4 is processed through the NCM. Thereafter, a sensitivity analysis is performed on the NCM parameters to identify the parameters the measurement is most sensitive to The tissue propagation model (TPM) is presented in Chapter 6 which models radiative transfer through the human body accounting for losses in the tissue a s well as dielectric mismatch. The NCM data is processed through the TPM towards an absolute temperature measurement. Lastly, the conclusions are drawn in Chapter 7 along with a discussion of the major findings of this investigation.
8 CHAPTER 2 A REVIEW OF MICROWAVE RADIOMET RY 2.1 Theory Microwave radiometry is a branch of microwave sensing which provides a passive sensing technique for detecting naturally em itted electromagnetic radiation. Microwave radiometers are highly sensitive wirel ess receivers which detect noise power radiated from objects in the form of brightness t emperature The power density ( P ) emitted by the object is proportional to its brightness (T B ) and physical temperatures (T phy ) as demonstrated in ( 1 ) where e is the emissivity of the object, k is Boltzmann's constant and B is the bandwidth of the power density. P = kT phy B T = T B e e = T B T Phy T B = P ekB ( 1 ) The theory of microwave radiometry originated in the 1920's when a scientist by the name of Max Planck discovered that all matter emits natural electromagnetic energy in his proof of Planck s Law". He also discovered that this emitted energy is proportion al to the frequency and temperature of the matter under investigation (MUI).
9 Planck 's Law ( 2 ) provides a relationship between emitted energy, frequency and temperature. Bf Planck = 2 hf 3 c 2 1 e hf kT 1 # $ % % & ( ( ( 2 ) Rayleigh Jean's Law is typically used in radiometric sensing applications, since it is an approximation of Planck's law, simplified for microwave frequencies. This is mainly due to the fact that the microwave band encompasses a small segment of frequencies within the electromagnetic spectrum (0 Hz 10 25 Hz), ranging from ~300 KHz 300 GHz. It is also important to note that Rayleigh Jean's Law is normalized to a particular temperature, usually 300 K (80 F) which is essentially ambient temperature and provides a lin ear relationship between brightness temperature and frequency. Rayleigh's expression is provided in ( 3 ) Figure 2 illustrates a comparison of Planck's curves and Rayleigh Jeans curves at normal body tem perature. Bf Rayleigh = 2 f 2 kT c 2 = 2 kT 2 ( 3 )
10 Figure 2 Comparison of Rayleigh Jean's law and Planck's law at normal body temperature 98 F 2.2 Biomedical Radiometric S ensing Microwave radiometers are likely to become common clinical instruments due to their vast range of applications such as oncology, surgery, gynecology, urology, mammography just to name a few   In particular, r adiometers are used in microwave thermo graphy as a means of generating thermal gradients of the MUI by quantifying the detected electromagnetic radiation which is in the form of emitted brightness temperature T B The emitted brightness temperature is dependent the electrical properties of the object under investigation; i.e. permittivity, permeability, and conductivity. With respect to biomedical sensing the permittivity or dielectric constant is the most important  Particularly the penetration depth is depend ent on permittivity as a function of frequency. In general, materials with a lower permittivity allow deeper sensing depths. As described in  other useful relations can be made between water/oxygen content and permittivity; 1.E-19 1.E-18 1.E-17 1.E-16 1.E-15 1.E-14 1.E-13 1.E-12 1.E-11 1.E-10 1.E-09 1.E-08 1.E-07 1.E+09 1.E+10 1.E+11 1.E+12 1.E+13 1.E+14 1.E+15 Brightness W/m 2 Hz sr Frequency (Hz) Planck's Curve @ 98 F Rayleigh Jean's Curve @ 98 F
11 such relations are the foundation for most microwave and radiometric sensors designed for biomedical sensing applications. Permittivity is a measure of how much energy an object stores or dissipates amid an electric field. Permittivity is a complex nu mber which varies with frequency; the real part denoting objects energy storage and the imaginary part representing the loss factor. In the presence of an electric field materials arrange their ions to receive energy from that field. The measure of how e asily the electric field vectors permeate through the object for a given area is the permittivity which is determined by dividing the electric flux (D) by the strength of the electric field (E), and is measured in farads per meter (F/m) ( 4 ) = D E ( 4 ) The emissivity e is a constant which ranges from zero to unity, with unity being the emissivity of a perfect emitter implying that all of the power from the object is emitted. A perfect electric conductor (metal) has an emissivity of zero, implying that no power is emitted, but conducted through the material. Fresnel's equations demonstrate the relationship between emissivity and the electrical properties (permitti vity) of human tissue ( 5 ) where & is the viewing angle of the sensor T his relation between power, emitted brightness temperature, and permittivity is expresses in, ( 1 ) ( 4 ) and ( 5 ) Similar relationships are used in analyzing biological data in biomedical microwave sensing  e = 1 # cos( $ ) # sin 2 ( $ ) # cos( $ ) # sin 2 ( $ ) 2 ( 5 )
12 2.3 Contact Radiometry A review of a few of the most significant contributions to on body radiometric sensors is presented in this section. These radiometers demonstrate successes in the areas of blood glucose monitoring, cancer detection, and neurology. Considering that the m ajority of the research in biomedical radiometric sensing has been done in the area of breast cancer detection, the RTM 01 RES was selected for this review since it is among the most extensively studied. Also presented is one of the most novel applicatio ns for the technology a microwave radiometer designed for blood glucose monitoring. The objective of this study is to present previous successes in on body radiometric sensing. 2.3.1 A Radiometric Sensor for Blood Glucose Monitoring This study begins with one of the most interesting applications of biomedical radiometric sensing, blood glucose monitoring. In  Laura Ballew and researchers from the Baylor School of Medicine developed a microwave radiometer capable of tracking changes in blood glucose levels. Previous authors (E.C. Green  ), have derived relations between blood glucose and permittivity. As stated in section 2.2 the brightness temperature is also related to permittivity. This work combines the relations between blood glucose, permittivity, and brightness temperature, and concludes that an increase in the radiometer brightness temperature is correlated to an incre ase in blood glucose levels. 18.104.22.168 Design and Specifications Ballew's radiometer is a superheterodyne receiver with a Dicke calibration scheme. A rectangular waveguide was used as the antenna. The design frequency was
13 chosen to be within 4.5 6.5 GHz, yieldi ng a penetration dept of 1 cm 1.5 cm This depth was chosen to facilitate the detection of blood flow in areas of low muscle content. The theoretical resolution of the radiometer is 0 .2 ¡C (~ 0 .36 ¡F) enabling the detection of subsurface temperature s w ith high accuracy. The device specifications were not measured, however the theoretical values are provided in Table 1 Table 1 Theoretical design specification of Ballew's radiometer Parameter Value Frequency of Operation (GHz) 4.5 6 .5 Pre Detection Bandwidth (MHz) 6 00 Depth of detect ion of thermal abnormality (cm) 1 1.5 Temperature Resolution ( ¡ F) 0 065 22.214.171.124 Measurement and Results The concept was demonstrated through the soda test, a standard experiment for blood glucose detection  To implement the soda test, the wrist of the patient is firmly placed at the input of the radiometer. As the patient co nsumes a soda the brightness temperature of the radiometer is tracked up to one hour before and after consumption. The results of the soda test are shown in  which demonstrate an apparent increase in the brightness temperatu re over time. A similar plot is presented in Figure 3 These results imply that the radiometer was able to successfully track changes in blood glucose levels. However an absolute blood glucose measurement was not attempted. This research proved that radiometers can monitor variations in blood glucose; however more research should be conducted before characterizing microwave radiometers as clinical blood glucose sensors.
14 Figure 3 The radiometer outpu t monitored as blood glucose level changes. The diagram was regenerated from  2.3.2 RTM 01 RES One of the most advanced radiometers developed for biomedical sensing applications is the RTM 01 RES, a computer based radiometer, ca pable of detecting abnormalities in human tissue and organs  The RTM 01 RES was initially developed in 1996 by RES LTD, a company based in Moscow, Russia. Since its initial development, this radiometer has been engineered for a wide range of applications such as urology, gynecology, surgery, mammography, and IR thermography. The RTM 01 RES has been most widely studied in the area of cancer detection, with most the work done in the area of breast cancer diagnosis. This is attributed to the fact that the RTM 01 RES can detect carcinoma in its pre clinical stages. Palpation, mammography and ultrasonography are traditional clinical diagnostics used to diagnose anatomical disparities in the breast. However, research has proven that anatomical disparities in human tissue are preceded by physiological variations (temperature 0 250 500 750 1000 0 1000 2000 3000 4000 5000 6000 7000 Radiometer Outout (uV) Times (S)
15 differentials). In fact temperature changes may be caused by inflammation and increased cell metabolism, and are associated with degenerating tissue. The R TM 01 RES detects these psychological variations by generating temperature fields of internal tissue to detect malignant carcinoma at pre clinical stages. 126.96.36.199 Design and Specifications The RTM 01 RES is a Dicke radiometer with null balancing and a slipping circuit to reduce fluctuations caused by interactions between the biological object and the antenna. The frequency of operation is 1.15 3.8GHz. The device specifications for the RTM 01 RES are quite impressive ( Table 2 ). The radiometer has a penetration depth from 3 cm 7 cm depending on the dielectric properties of the tissue. The measurement range of internal tissue and organs ranges from 32 ¡C 38 ¡C, which equates to 89.6 F 100 F. The resolution of the radiometer is 0.2 ¡C (~0.36 ¡F) enabling the detection of temperature differentials with high accuracy. Table 2 RTM 01 RES device specifications. Parameter Value Frequency of Operation (GHz) 1 3.5 Pre Detection Bandwidth (MHz) 100 Depth of detection of thermal abnormality (cm). 3 7 Temperature Resolution ( ¡ F) 0 .36 Measurement Range ( ¡ F) 90 100
16 188.8.131.52 Measurement and Results This section provides results from a RTM 01 RES diagnosis of breast cancer. The procedure is implemented with the patients lying on their backs with their hands behind their head, in order to normalize the positions of the measurement points of interest (flatten the breast). Ten evenly dis tributed diagnosis points on each breast are measured: the areola, centers of the quadrants, borders between the quadrants and auxiliary regions. The antenna is heated to the temperature of the subject for contact sensing, to bring the patients body tempe rature to a homogenous state. If the patient feels cold or uncomfortable the measurement could be distorted. The antenna is gently contacted on each of the points of interest for 20 s 30 s on each breast. To maintain reliability, the points of intere st are measured sequentially on the left then right breast. If the temperature differential between the investigation points of the left and right breast is more than 0.8 F, there is a possibility of an error and the measurement procedure should be repe ated. If such differentials are consistent, there is a high probability of abnormalities such as carcinoma in the breast, and or measurement area of interest. The following diagnosis denotes a high risk of breast cancer: 1) Increased thermal differential s between the corresponding of the left and right breast. 2) Increased thermal differentials between sites on the same breast. 3) Higher dispersion of the temperature differential between the left and right breast. 4) Differentials between the nipple sites of the breasts.
17 5) High ductal (nipple) temperature in the damaged breast in comparison with average breast temperature, with respect to age. Examples of internal temperature distributions for normal and cancerous breasts are shown in Figure 4 The right breast is diagnosed with ductal (nipple) cancer, and illustrates an elevated temperature in the ductal (middle) region of the breast. Figure 4 Thermal distribution of a healthy (left) and cancerous (right) breast. The diagram was regenerated from  The RTM 01 RES also has implications in neurology particularly in the treatment and monitoring of muscular disorders and the detection of spinal abnormalities. Figure 5 illustrates application of the RTM 01 RES in neurology by distinguishing spinal abnormalities. The red (dashed) line is a thermogram of a deforming spondileus of a 67 year old patient, which is compared with a thermogram of a healthy 21 ye ar old patient with no abnormalities (blue).
18 Figure 5 Thermogram of a deformed (red dashed ) and healthy spine ( blue ) 2.4 Limitations of the Contact Radiometry Though on body radiometric devices have been successful as biomedi cal sensors, there are some drawbacks that justify the need for a non contact approach in certain applications. R ecent studies (2006 present) have shown that there are several deployment issues specific to the on body convention which may or may not be ne gligible depending on the application   For instance, thermal conduction between the tissue and sensor can induce measurement uncertainties by distorting the temperature profile when the s ensor is placed in direct contact with the body    On body sensors are also uncomfortable and may cause skin contusions under conditions of extended use. Additionally, p lacing the antenna in direct contact with the tissue under investigation ( TUI ) creates near fi e ld diffusion wherein the detected field s are scattered throughout the TUI  In the principle of c ore body temperature extraction, near field 90 92 94 96 98 100 C1 C3 C5 C7 D2 D4 D6 D8 Temperature (F) Spin Number Healthy Spine Deforming Spine
19 diffusion limits the sensing depth which leads to detect ion of signals from areas closer to the tissue surface rather tha n the core. Though the area of maximum detected field strength is normal to the antenna with the expected G aussian shaped contour thermal emissions from random areas within tissue induce measurement errors due to the degraded sensing depth The recorded detection depths of actual on body sensors are well below the theoretical limit, which could be partly due to th e near field diffusion phenomenon  The diffusion phenomena may be tolerable in cancer detection and or imagin g applications where the brightness temperature of the specimen (i.e. cancer, brain activity, glucose variations) is distinguishable being that its dielectric properties create stronger emissions than the surrounding tissue  Though diffusion limits the detection depth, emissions from the specimen are 25% 35% stronger than the surrounding tissue and therefore detectable closer to the surface. However, in core body temperature extraction the dielectric properties of the tissu e layers are relatively uniform across the lateral sensing profile. As a result the detected emissions are a function of the physical temperature of the specimen, which is at most 4% stronger than the surrounding tissue. Considering that healthy body temp erature is approximately 98.6 F with a dynamic range of 4%, the human core emits weaker brightness temperatures that are difficult to detect due to the uniform dielectric profile of surrounding tissue. Therefore the degraded depth of detection induced by diffusion considerably impedes the ability to detect weaker subsurface temperature differentials emitted from the human core. Hence it can be argued that a non contact approach is necessary to mitigate sensor placement issues, reduce measurement uncerta inty, and enhance detection depth.
20 2.5 Non Contact Radiometric Sensing Recent successes in non contact radiometry support the technological feasibility for true, non invasive biomedical sensing   As of late (2002 current), promising results have been achieved via remote (in this case, d < 0.8 m) monitoring of thermal and electrical conductivity variations of muscle and brain phantoms. In  a radiometric system is employed for intracranial imaging consisting of a directional antenna and/or array, and a large ellipsoidal cavity (1.5 m) for focusing microwave energy into the desired regions of the brain A conformal antenna array and matching material between the antenna and specimen theoretically improves beam focusing to adequate detection depths fo r subsurface field imaging; the thickness of the matching material is crucial for optimal performance   Of the current non contacting modalities virtually none embody close proximity detection capabilities. The majority of the close proximity and near field measurement studies are in the preliminary stages, encompassing only simulation, theoretical, and conceptual demonstration None of the previous studies have demonstrated an absolute subsurface temperature measurement at a range of a few centimeters from the TUI. The deficiency of a solid knowledge base within this area is essentially attributed to certain propagation challenges, which occur in the reactive antenna body near field ( Figure 6 ) such as electromagnetic (EM) field dispersion, antenna resonance shifts, bandwidth degradation, and impedance mismatch. Many authors have stated that these propagation challenges in the human body near field create daunting instabilities   Others have identified these challenges as significant but very few solutions ha ve been offered, other than to follow the on body convention.
21 Figure 6 Radiometric sensor positioned in the near field of a human core model (HCM). In  the near field dispersion phenomenon is explained and potential solutions are presented. The potential of close proximity brain imaging is investigated through simulation of electromagnetic field images across a cranium model. The latter demonstrates met hodologies for maximizing resolution, detection depth and sensitivity by means of application specific antenna design and proper antenna offset distance. Subsequent conceptual (simulation) studies imply that displacing the antenna precisely 1 0 m m 20 m m from the specimen further improves the detection depth and pattern contour, beyond that of the matching layer approach mentioned in  These simulations also demonstrate that precise offset minimizes near field diffusion. T hough the results were p romising, in depth experimental studies are still necessary to characterize close proximity radiometry as a viable biomedical sensing methodology.
22 CHAPTER 3 PRELIMINARY STUDY: T HE 1 ST GENERATION DESIGN A conceptual demonstration of close proximity biomedical radiometry is demonstrated in this preliminary study of a total power microwave radiometer (TPR). The sensor is projected to be integrated into the uniforms of servicemen or as a hand held device. Therefore, the radiometer and test bed are designed to replicate a health sensor positioned in close proximity (7 mm 35 mm) to human tissue. The TPR was chosen for this initial study due to its relatively simple design which has been well studied in a b road range of non invasive and or remote sensing applications; geo science, remote monitoring of high temperature materials, and biomedical monitoring   It is also the baseline design for more advanced radiometer architectures such as Dicke Hach and noise injection  This pool of prior knowledge reduces the number of unknowns when correlating the biomedical requirements of the close proximity approach to th e sensor design parameters. In essence, some performance specifications can be estimated based on previous works For instance, the TRR is designed for high resolution, with minimal components, which are desired characteristics for a stand alone or integrated he alth monitoring device  The drawbacks are sub optimal accuracy and measurement uncertainty caused by gain drifts and instability in the low noise amplifiers  Previous studies have proven that these phenomena can be mitigated through,
23 external calibration, device miniaturization and or thermal stabilization which will be implemented in Chapter 4. One of the most significant contributions of this work is an analysis of the non c ontacting nature of the sensor, which presents certain challenges that have been identified as substantial obstacles by previous authors (e.g.   ). Some of the most problematic design challen ge s are related to antenna performance degradation, as the antenna comes in close proximity to and or touch es the body  These phenomena are demonstrated by analyzing the performance characteristics of a printed dipole ante nna in the near field of a blood fatty tissue phantom. We propose various antenna design methodologies and near field models to compensate for these effects. Until this work, very few solutions have been provided other than to follow the on body conventi on, and none of the proposed non contacting methodologies are feasible for a stand alone device, capable of real time physiological monitoring. Measurement and testing is performed on the test bed, which consist s of a tissue phantom with the electrical pr operties (dielectric constant $) similar t o human tissue with in the spectrum of 1 GHz 2 GHz, which covers the frequency band of the TPR I n this initial study, we are particularly interested in noninvasively tracking temporal changes in a blood fatty tissue phantom to demonstrate proof of concept. T issue phantoms that mimic skin and muscle have also been identified to provide a more accurate model of the body. T he applications of thes e phantoms models are limitless; biomedical telemetry devices, non contact wireless sensors and wearable devices just to name a few As the work progresses, layered configurations of these tissue phantoms will be configured to model the body's clinical diagnostic points, where the sensor is
24 expected to be positioned. Th ese enhancements improve the accuracy of the test bed towards a clinical trial comparison However the scope of this preliminary study is to first conceptually prove that biological data can be extracted from a simplified measurement test bed via close pr oximity total power radiometer measurements identify the artifacts which obstruct the measurement, and provide solutions to mitigate these artifacts 3.1 A TPR Design ed for Biomedical Sensing Applications The TPR design consists of an antenna, RF front en d, down conversion stage, low frequency circuitry and a voltage detector for rectification. A block diagram of the TPR design is presented in Figure 7 The overall dimensions when placed inside of a metal enclosure for thermal sta bilization are 50 cm x 9 cm x 4 cm. The sensor is essentially a high gain (~70dB) receiver that detects thermal emissions radiated from human tissue, which can be related to core temperature. The 1.4 GHz design frequency ( f c ) enables an acceptable detect ion depth; up to 30 mm into muscle and blood, and 90 mm into fatty tissue  The antenna is a printed dipole (PD) in a non metal cavity designed at 1.4 GHz, with a 400 MHz bandwidth. The next stage is the RF front end, a super heterodyne receiver with the following components: multi port RF switch, isolator, low noise amplifier, and band pass filter. The switch connects to the antenna and two broadband (1 GHz 18 GHz) reference temperature loads. Through calibration the reference loads are used to relate the signal at the radiometer input to an absolute temperature. A 50 termination submersed in cryogenics (liquid nitrogen) is used for the cold load (77 K), while an attenuated diode
25 noise source is used for the hot load (~7618 K). The isolator attenuates unwanted noise emanating from the radiometer in the direction of the antenna, which may reflect off the specimen and or fe e d back into the system input. Next, the RF LNA is chosen to have a very low noise figure (NF < 0.6 dB), since the NF determines the input noise temperature of the first amplifier, which has a substantial effect on the overall noise temperature of the receiver (T' REC )  A noisy system can cause degradation in a ccuracy and precision since T' REC is inversely proportional to the sensor resolution ( ( T) In particular T' REC and ( T are related by ( 6 ) where ) and T' A are respectively, the sensor integration time, bandwidth, and noise temp erature of the antenna. For this reason, a very low noise amplifier at the radiometer front end maximizes ( T. High resolution sensors are vital for extracting subsurface tissue temperature, due to the fact that the dynamic sensing range could be as low a s 10 F 15 F This range becomes even smaller, in the case of core body temperature extraction, as heat related disorders are diagnosed at 5 F from homeostasis, 98.6 100 F However, the primary function of the radio frequency ( RF ) low noise amplifier (LNA) is to aid in distinguishing the minimal detectable signal from the noise floor, by amplifying the emissions f rom the tissue under investigation (TU I ). Since the human body temperatures are very close to that of ambient temperature, the RF LNA is chosen to have a high gain (30 dB) within the sensing band of interest (1.1 GHz 1.6 GHz). After amplification and filtering, a mixer with a 1.1 GHz local oscillator (LO) frequency performs double s ideband down conversion to the intermediate frequency ( IF). The low frequency circuitry consists of a low pass filter and two 21 dB gain IF LNAs, and is used to eliminate harmonics induced by down conversion and amplify the input
26 signal to a suitable level for subsequent rectification. At this sta ge in the system the IF band is DC 4 00 MHz. A DC b l ock is added to protect the preamplifier from LO harmonics generated from down converting In the final stage, a Schotty diode is used for rectification of the IF band into a DC output voltage, proport ional to the noise temperature at the radiometer input. T he magnitude of the output voltage is then related to the intensity of the bri ghtness temperatu re of the tissue under investigation (TUI ), t hrough calibration T = T A + T REC # $ ( 6 ) Figure 7 Block diagram of the TPR. 3.2 Calibration The TPR employs an internal calibration methodology, wherein h ot and cold reference s are measured to generate calibration curves. The calibration curves in Figure
27 8 were generated by two methodologies. It is important to note that the voltage offsets in the calibration curves in Figure 8 are likely due to positive amplification of the negatively polarized rectifier output. The f irst calibration methodology (CM1) makes use of a diode noise source for the hot load and a 50 load immersed in liquid nitrogen as the cold load. The reference noise temperature of the noise source and cold load are 1065 K and 77 K respectively. A second calibration methodology (CM2) is implemented for comparison purposes, which uses a variable attenuator and a noise source, in which multiple calibration points are generated corresponding to temperatures ranging from 295 K 7618 K. Theoretical ly if there are no gain variations in the system the calibration curves and equations for CM1 and CM2 should be identical. However, our results showed some variation in the slopes (system gain): 5.7 mv/K for CM1 and 4.9 mv/K for CM2. As a result gain var iations are expected, which are likely due to suboptimal thermal stability of the front end components. Since the total system gain is ~70dB, a small variation in gain could result in significant measurement uncertainties Hence continuous calibration, an d system stabilization are critical to achieving optimal accuracy and therefore will be included in 2 nd generation sensor design.
28 Figure 8 Calibration curves of the TPR. 3.3 Antenna Requirements for Biomedical Radiometric Sensi ng A ntennas designed for biomedical radiometric sensing are preferred to be high efficiency, directional radiators with broadband characteristics A relatively compact directional radiator is preferred for targeted sensing of human tissue, organs, and o r clinical diagnosis points ( i.e. wrist blood pressure, chest heartbeat, core body temperature ). Though the size of the aperture is proportional to the directivity of the radiation pattern, it is inversely proportional to the frequency of operation which d etermines the sensing/detection depth. As a result there is a tradeoff between the antenna size, directivity and sensing depth. A broadband antenna enables maximum temperature resolution, which is critical in detecting subsurface emissions from interna l tissue and organs. ( 1 ) defines the resolution and or minimum detectable signal of a radiometric receiver; where T` A T` REC -10 -8 -6 -4 -2 0 2 4 0 50 100 150 200 250 300 350 400 450 500 550 600 Output (mV) Temp (K) CM1 Cal CurveLoads CM2 Cal CurveAttenuator
29 ) and are respectively the radiometric temperature detected by the antenna, system noise temperature, integration time, and bandwidth. T = # T A + # T REC $% ( 7 ) The sensor designer has very little control over T` A ) is the time needed for an accurate measurement of the TUI. Thus for the sensor to achieve high resolution, the antenna should be designed such that is wideband at the sensor design frequency. The antenna should also exhibit a high efficiency which is c ritical in detecting low emissions from internal tissue. Any reduction in signal integrity caused by the antenna significantly degrades the accuracy of the sensor. Furthermore, a n antenna with low efficiency heightens front end system loss by increasing T` REC T' REC depends largely on the loss in the receiver front end and should be minimized to achieve maximum temperature resolution. Therefore a highly efficient antenna is preferred for optimal sensor resolution and accurate detection of weak emissions generated from human tissue. 3.4 The Printed Dipole Antenna (PD1) A 1.4 GHz half wavelength printed dipole was selected for the TPR because it is a widely studied, compact, broadband aperture with a relatively simple de sign  In our case a fairly compact, planar structure is preferred for ease of integration into uniforms or for deployment as a hand held device An in depth analysis of the 1 st generation printed dipole antenna (PD1) is p resented in this section. Figure 9 provides an illustration of PD1, which is designed using the Momentum full wave electromagnetic simulator in Agilent's Advanced Design System (ADS). The front, side, and rear views of the
30 antenn a are shown in Figure 10 and the dimensions provided in Table 3 The dipole arms are each + /4 electrically, which is equivalent to a physical length of approximately 42 mm. The arms are fed by a + /2 bal un, which in theory balances the amplitude and phase of the current distribution between the dipole arms. 3.4.1 Characterization The free space characterization in Figure 11 and Figure 12 shows that there is a very good agreement between the measured and simulated resonance, bandwidth (250 MHz), reflection coefficient (S11), and radiation pattern. As a result it can be inferred that the simulated and measured radiation characteristics (gain, directivity, and efficiency) are also comparable; thes e values are provided in Table 4 Figure 9 Momentum simulation of PD1.
31 Figure 10 Front (left), side (middle), and back (right) views of PD1. Table 3 Dimensions of PD1. !"#$ %&$ #'()*+$ ,-*./$ %&$ 0.1234-3+$ ,-56$ 74)/3$ 0'8+$ Parameter Value Overall Dimensions L xWxH (mm) 70x11 0 x0.8 Height / Substrate Thickness (mil) 31 Length of + /4 Dipoles (mm) 42 x2 Length of Balun + /4 Short and + /4 Open (mm) 30.3 x2 Ground LxW (mm) 32x19
32 Figure 11 Meas u red versus simulated S11 of the printed dipole antenna in free space. Figure 12 Measured versus simulated normalized radiation pattern of PD1 in dB scale. -45 -40 -35 -30 -25 -20 -15 -10 -5 0 1 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2 S11 (dB) Freq (GHz) PD1 Free Space Sim PD1 Free Space Meas -60 -40 -20 0 0 90 180 270 PD1 Free Space Meas PD1 Free Space Sim
33 Table 4 PD1 a ntenna characteristics 3.4.2 Body Effects As the antenna comes into the near field of the body, the antenna characteristics are distorted Figure 13 demonstrates resonance shifts and antenna input match degradation, which arise from the antenna being at short distances (7 mm 35 mm) from the TUI More specifically, when the TUI sensor offset is varied from 7 mm to 35 mm, the resonant frequency shi fts from the 1.4 GHz design frequency to 1.5 GHz. Any divergence from f c degrades the IF band input into the detector which subsequently reduces resolution, and in this case the depth of detection. In addition, the magnitude of the resonance is degraded by ~10 dB which would result in signal loss of at least 10% at the air antenna interface. Most importantly, the bandwidth decreased from 250 MHz to 150 MHz when the antenna was brought within 7 mm of the TUI, which will degrade the sensor resolution, by a factor of at least 2. These characteristics will vary depending on th e antenna, yet such losses considerably obstruct the accuracy of the sensor. Parameter Value Resonant Frequency (GHz) 1.45 Gain (dB) 1.56 Directivity (dB) 2.45 Efficiency (unit less) 0.85 Bandwidth (MHz) 250
34 Figure 13 Antenna S11 degradation versus offset distance from the phantom 3.4.3 Cavity Effects The printed dipole generates an omni directional radiation pattern ( Figure 12 ), though a more directive pattern is desired in biomedical sensing applications  A directional pattern could be achieved by adding a ground plane behind the dipole but the tradeoffs would be degraded bandwidth and increased aperture size, which are both undesirable characteristics for antennas dep loyed in biomedical applications  For this reason a non metal cavity was designed to isolate the antenna from background radiation ( Figure 14 ). The cavity is comprised of Plexiglas, and lined with a near field absorbing material (supplied by ARC technologies 1 ) designed to suppresses unwanted side and back lobe contributi ons by a factor of 20 dB. The ca vity is adjustable such that tissue sensor offset can be varied from 0 mm to 60 mm, enabling characterization of the sensor and antenna at distances representative of a health monitoring device inside of an astronaut's un iform. 1 ARC Technologies 11 Chestnut Street Amesbury MA 01913
35 Figure 14 Non metal cavity used for the printed dipole antenna Figure 15 Bottom (left) and top (right) views of the PD1 in side the c avity Si nce the cavity itself induced changes in the antenna performance, the original printed dipole (PD) was redesigned (PD RE ) for optimal performance inside the cavity, by matching the impedance of the balun feed and tuning the dipole lengths for frequency selection. The orientation of the antenna inside the cavity is illustrated in Figure 15 The best performance was achieved with the antenna inset 6 cm inside cavity. Figure 16 shows the degraded S11 responses of PD1 in the cavity and the improved respon se of PD RE The dimensions of PD and PD RE are described in Table 5 !"# Rubber Stopper Plexiglas Cavity Levitation Screws Antenna Holders Near Field Absorber !"# $#%"# $#%"#
36 Figure 16 Cavity effects of PD1 versus PD RE Table 5 Dimensions of PD and PD RE 3.5 Measurement Test Be d In order to benchmark the performance of non invasive biomedical sensors reconfigurable phantom models are needed which are capable of mimicking the physical and electrical properties of the tissue across the sen sing depth The body is a complex system, consisting of skin, muscle, blood and fatty tissue, with dissimilar electrical and physical properties. As a resu lt, each tissue layer will affect the performance of the -60 -50 -40 -30 -20 -10 0 1.0 1.2 1.4 1.6 1.8 2.0 S11 (dB) Frequency (GHz) PD1: Free Space No Cavity PD1: 6cm Inside Cavity PDre: 6cm Inside Cavity Parameter PD PD RE Overall Dimensions LxW (mm) 70x110 70x110 Substrate Thickness (mil) 31 31 + /4 Dipoles Length (mm) 42x2 47x2 Length of Balun + /4 Short and + /4 Open (mm) 30.3x2 30.3x2 Ground LxW (mm) 32x19 32x19
37 sensor. Therefore, discrete phantoms, which model only one tissue layer at a time, do not provide the best replica of the body. To accurately depict the electrical profile of the TUI layered phant om models must have a form factor similar to that of the tissue volume. In t his work various tissue phantoms have been developed and characterized which mimic the electrical properties of the intervening tissue layers of an abdominal cavity within the f requency band of 1 GHz 2 GHz. However, only the blood phantom was used for simplification of the radiometric temperature measurement in this proof of concept demonstration. The phantoms were characterized with respect to complex dielectric constant us ing the Agilent 85070E dielectric probe kit, and the results compared to the Gabriel model, which is used as the standard for human tissue characterization  Since the tissue impedance is an important parameter for characterizing on body sensors and near field antenna performance, the impedance of the phantoms were also calculated and presented in the analysis. 3.5.1 Blood Fatty Tissue Phantom Herein blood fatty t issue was simulated using a mixture of h ydroxethylcellulose ( HEC ) salt, sugar and water the most prominent compounds in human blood as well as fatty (cellulo se, salt, water) tissue ( Table 6 )  To model blood and fatty tissue inside the stomach a weighted average of the dielectric properties of the tissue is applied, assuming 12% body fat and 88% blood, which results in a die lectric constant of 53 and an impedance of 50% at f c Figure 17 outlines the development process, and the recipe is
38 provided in Table 8 A s illustrated in Figure 18 and Figure 19 the blood phantom has a dielectric constant of 54 and impedance of 51 at f c which is equivalent to the findings of Gabriel and others in the literature. Table 6 Recipe for blood fatty tissue phanto m  Ingredients % By Weight Water 56 Sugar 0.76 Hydroxylethylcellulose (HEC) 41.76 Salt 1.21 Bactericide 0.27 !"#$%"&'%()*+"#),%-),"#,+)+(*.%"&$)+/&)+"%"&'%0'1'*)23',"%2$)-'((4% 5'6"%76"'$%")% 8)#*#,/%2)#,"4% 900%(+/6$% 6,0%(6*"4%% :),"#,+'%")%8)#*%"&'% ()*+"#),%+,"#*%"&'% -)32)+,0(%6$'%0#(()*1'04%% ;'0+-'%&'6"<%6,0%-),"#,+'% ("#$$#,/%+,"#*%"&'% -)32)+,0%#(%0#(()*1'04% =&'%(632*'%#(% ,)7%2$'26$'0%>)$% -&6$6-"'$#?6"#),4% 900%5@:%% Figure 17 Development process for the blood fatty tissue phantom.
39 Figure 18 Comparison of the real ( # r ) and imaginary ( # '' r ) dielectric constant ( # r ) of the blood fatty tissue phantom to the Gabriel model. Figure 19 Comparison of the blood fatty tissue phantom impedance (Z) to the Gabriel model. 45 46 47 48 49 50 51 52 53 54 55 1.0 1.2 1.4 1.6 1.8 2.0 Z ( ) Freq (GHz) Z Blood Phantom Z Blood Gabriel
40 3.5.2 Hybrid Skin Muscle Phantom Presented is the first hybrid skin muscle phantom in a solidified composite form. As described in the introduction, the majority of the current tissue phantoms are discrete materials, usually liquids, whereas the human body is compromised of layered volumes of interconnected solids as well as liquids. Composite or hybrid phantoms provide a more accurate model of the body's clinical diagnostic points, which is important in improving the precision of the measurement test bed, as it is very difficult to model such a complex biological sy stems as the human body. Solid phantoms can be shaped into three dimensional volumes of human tissue without the support of casts or containers which may alter the relative dielectric, and or impedance profile of the phantom. The skin muscle phantom in Figure 20 is developed using a simple mixture of 44% water and 56% TX 151, provided by the Oil Center Research 2 The process is presented in Figure 21 and the recipe in Table 7 The surface of the hybrid phantom mimics damp skin, to account for perspiration in conditions of extreme heat and or condensation deposits in cold environments The skin layer has non uniform thickness, ranging from 1 mm 2 mm, which is comparable to th e combined thickness of the dermis, epidermis, and hypodermis. The muscle layer is located immediately below the skin layer, and also has a non uniform thickness of 7 mm to 8 mm. The electrical characteristics of the skin and muscle layers a re presented below in Figure 22 Figure 25 When preserved in an airtight enclosure, the electrical and physical characteristics of the phantom will remain relatively stable for at least 6 months. 2 Oil Center Research, 616 W. Pont Des Mouton Road, Lafayette LA 70507
41 Figure 20 The hybrid skin muscle phantom Figure 21 Development process for the hybrid skin muscle phantom. Table 7 Recipe for hybrid skin muscle phantom. 55 mm Muscle Phantom Skin Phantom 7 8 mm 1 2 mm !"#$#%"$&%'(#)*$+,-$.(#/0$'$ #%/($1%/#"$2/0*$3)4",5$#%"$ 5.,6'3"$)6$#%"$&%'(#)*7$$ 8"'#$1'#",$#)$ 9)/0/(:$&)/(#7$ ;++$<=>?@?$ A("'+$#%"$5)0.#/)($ .(#/0$B'00C$<=>?@?$ &',#/30"5$',"$5%'&"+$ /(#)$'$5/(:0"$5)0/+$6),*7$ <%"$5'*&0"$/5$()1$ &,"&',"+$6),$ 3%','3#",/D'#/)(7$ Ingredients % By Weight Water 60 TX 151 40
42 Figure 22 Comparison of the real ( # r ) and imaginary ( # '' r ) dielectric constant ( # r ) of the skin phantom to the Gabriel model Figure 23 Comparison of the skin phantom impedance (Z) to the Gabriel model 50 52 54 56 58 60 1 1.2 1.4 1.6 1.8 2 Z ( ) Freq (GHz) Z Skin Gabriel Z Skin Phantom
43 Figure 24 Comparison of the real ( # r ) and imaginary ( # '' r ) dielectric constant ( # r ) of the muscle phantom to the Gabriel model. Figure 25 Comparison of the muscle phantom impedance (Z) to the Gabriel model. 3.6 Measurement Results Referring to the measuremen t setup illustrated in Figure 26 the temperature of the blood phantom was varied as the radiometer monitored the brightness temperature with 10 15 20 25 30 35 40 45 50 55 60 10 15 20 25 30 35 40 45 50 55 60 1.0 1.2 1.4 1.6 1.8 2.0 r '' # r Freq (GHz) # r Muscle Gabriel # r Muscle Phantom # r '' Muscle Gabriel # r '' Muscle Phantom 45 46 47 48 49 50 51 52 53 54 55 1 1.2 1.4 1.6 1.8 2 Z ( ) Freq (GHz) Z Muscle Gabriel Z Muscle Phantom
44 the PD RE positioned facedown inside the cavity, parallel to the TUI offset ~25 mm from the phantom ( Figure 15 ). The physical temperature is tracked using an infrared thermometer (IR) at the surface of the phantom and a digital thermometer (DT) located internally, at a depth of ~50 mm. In an effort to simulate a drop in core body temperature, the phantom tempera ture was varied from 111 ¡ F to 65 ¡ F, which is just outside the dynamic range of human body  Human core temperatures (T c ) in the range of 93 ¡ F < T c < 101 ¡ F are considered normal. Temperatures outside this range are consi dered adverse with T c < 93 ¡ F being Hypothermic, and T c # 102 ¡ F considered exhaustion or heat stroke. An analysis of the experimental data, showing the comparison of temporal var iations between the TPR, the IR and the DT, is provided in Figure 27 The curves in this figure are normalized to the initial temperature reading of the TPR The internal and surface temperatures of the phantom are virtually identical which implies that the phantom temperature is uniform throughout. T he similarities in the curves prove that the TPR indeed demonstrates the general ability to track changes in tissue temperature from the near field of the TUI. However, there are some differences in the morphology of the TPR curve as compared to the IR an d DT. In particular, t he slope changes in the radiometric curve exhibited in time intervals 3 and 6 are likely due to spurious signals detected in the antenna back lobe They could also be an effect of amplifier gain drifts which were predicted from the results of the calibration analysis in section 3 .2 In addition the radiometric measurement appears to be colder than the IR and DT which is likely due to factors relating to the non contacting nature of the sensor, e.g., r efl ection loss at the antenna input, back/side lobe contributions, air skin reflections, noise radiated
45 by the receiver, and the emissivity of the sp ecimen. T hese artifacts contribute to the radiometric measurement and are heightened in close proximity sensing applications. Figure 26 1 st g eneration m easurement test bed. Figure 27 Results normalized p hantom measurements: TPR vs infrared t hermometer (surface) and digital t hermometer (internal). 0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1 2 3 4 5 6 7 8 9 10 Normalized Temperature Time Intervals (15s-45s) TPR F DT Internal IR Surface
46 3.7 Conclusion Presented is the initial development of a radiometric sensor for noninvasive, close proximity biomedical monitoring. Although the ability to track temporal changes in the specimen temperature has been qualitatively demonstrated, certain phenomena have been identified which distort close proximity radiometric measurements. The measurement results imply that absolute specimen temperature extracti on is plausible, however a mathematical model is necessary to account for certain artifacts which arise due to the non contact ing nature of the sensor. S olutions in the area of antenna design are provided by implementing an absorbing cavity to suppress unwanted radiation opposite the TU I, and designing the antenna for optional functionality in close proximity to the body We have also identified receiver instability characteristics which are represented by the variations in the slopes of the calibration curves and are likely due to thermal drifts in the RF components. The proposed solutions are a miniaturized design with an enhanced calibration scheme and thermal stabilization. Hence a 2nd generation design is presented in CHAPTER 4 which incorporates continuous calibration to mitigate receiver instabilities and an improved antenna design to compensate for the near field effects
47 CHAPTER 4 2 ND GENERATION DESIGN This chapter presents various enhancements to the sensor and antenna design to mitigate certain artifacts which obstruct the close proximity measurement Experimentation and testing are performed on an enhanced measurement test bed a multilayer phantom model which mimics a three dimensional volume of a n abdom inal cavity The modifications to the 1 st generation sensor facilitate s improved accuracy and resolution by means of a miniaturized design which incorporates a continuous calibration scheme T he most noteworthy enhancement is the 2 nd generation antenna in which it s novel ty lies within the performance characteristics that aid in preserving the functionality of the sensor in the antenna body near field 4.1 Design of a Microwave Radiometer for Biomedical Sensing (MRBS) The ( MRBS ) is a continuous calibrating TPR with direct conversion ( D C ) in phase (I) qu adrature (Q) demodulation, I/Q. When compared to the superheterodyne based TPR, the advantages of the D C I/Q architecture are reduced cost, power consumption, radio frequency components, and high linea rity  M ost importantly, the architecture is well suited for miniaturizatio n. These characteristics are ide al for the intended application, a stand alone health monitoring device, integratable into the uniforms of astronauts or servicemen for core body temper ature monitoring
48 The design consists of a cavity backed slot antenna (CBSA)  RF front end, and I/Q channels with an integrated rms detector. The block diagram is shown in Figure 28 Analogous to the TPR, the MBRS design frequency is 1.4 GHz which in theory, provides sensing depths up to 30 mm through ski n muscle tissue  enabling the measure ment of the blood temperature beneath the abdominal cavity. The antenna is a CBSA, designed for optimal functionality in close proximity to the body. The front end consists of a multi port RF switch, isolator, low noise amplifier, and band pass filter. The switch connects to the an tenna and three reference temperature loads. A 50 % termination at room temperature is used for the cold load ( 71 F ), while an attenuated diode noise source is used for the hot load ( 235 F ). The third standard is an open circuit, which is used to determine the noise temperature generated by the ra diometer in the direction of the antenna (T REV ) and or reflected back into the system (T' REV ) An L Band isolator is used to attenuate T REV while in effect the noise temperature of T' REV is equivalent to the physical temperature of the isolator The final component in the RF front end is the band pass filter which has a center frequency of 1.4 GHz with a 100 MHz bandwidth. The band pass filter attenuates spurious signals outside of the sensing band of interest and passes the signal contributions emi tted across the targeted detection depth. After amplification and filtering the signal is equally divided into the I and Q channels for D C demodulat ion ( LO = f c ) and subsequent rms rectification to DC output voltage s The schematics of the I/Q chan nels are equivalent to the lo w frequency circuitry in the first generation design presented in section 3.1 In general, I/Q demodulation involves direct conversion D C at the design frequency ( f c ) via two
49 mixers with the local oscillator frequencies synchronized to f c and 90 out of phase, thus the term in phase quadrature. As a result the image frequency is centered at 0 Hz and both positive sidebands are preserved in the I and Q channels as the negative sidebands and respective harmonics are canceled and or filtered. In theory the I and Q outputs are combined to reconstruct the double sideband signa l, however only one channel is considered in this study for simplification Compared to th e TPR architecture the overall size reduction of the MRBS allows for enhanced stability, resolution and accuracy The dimensions of the MRBS are 22 cm x 6.3 cm x 4 cm which equates to a size reduction of about 50 %, when compared to the 1 st generation TP R (50 cm x 9 cm x 4cm) initially presented in section 3.1 Thermal stabilization is more efficient and easier to implement on smaller devices with fewer components, as a result the accuracy of the sensor is improved substantial ly Thermal stability of the MRBS is achieved by a metal enclosure T he signal transmission path is also shortened which reduces front end losses that contribute to the receiver noise temperature (T' REC ) The result is improved resolution, as T' REC and ( T are inversely proportional ( 6 )
50 Figure 28 Block diagram of the MRBS. 4.2 Calibration C ontinuous calibration is imple mented in the MRBS design which minimizes measurement uncertainty and improves resolution. When compared to the TPR, in which only one calibration cur ve is generated per experiment, the MRBS generates a calibration curve for each T B measurement. In effect each data point is extracted with optimal precision given that th e noise temperature of the calibration standard s are know to a high degree of accuracy. As described in the previous section, three standards are measured during each calibration cycle; hot T H cold T C and open T O The time interval for each cycle, incl uding the s pecimen temperature T SC (TUI ) is approximately 1.3 s. The results is a substantial reduction in the allowable time window for gain drifts in the RF components which in turn minimizes measurement uncertainty Continuous calibration also enable s the detection of small temporal changes in the TU I and therefore improves ( T. I Out V rms I Circuitry Q Circuitry Q Out V rms Quad Coupler 1.4 GHz LO Power Divider Cold (C) RF Switch Iso BPF AMP Hot (H)
51 4.3 A Cavity Backed Slot Antenna (CBSA) for Near Field Biomedical Radiometry The most noteworthy enhancement o f the 2 nd generation sensor is the antenna; a cavity backed slot antenna (CBSA) designed to satisfying the requirements for near field human body detection By combining the advantages of annular slot and cavity backed antennas, the CBSA is designed to compensate for o bstructive antenna body effe cts, initially demonstrated in section 3.4.2 of the preliminary study T he antenna is a d irectional, broadband radiator, desig n at 1.4 GHz. It is also frequency tunable and or reconfigurable for implementation in other biomedical sensing applications. Although spiral, patch, array, and other antennas commonly used in biomedical sensing applications were considered, the performance characteristics of cavity and annular ante nnas are best suited for the close proximity ap proach and provide better design flexibility. Multiple degrees of freedom in the antenna design are desired, mainly due to the varying performance characteristics in the near field of the body. With respect to sensor performance, t he main advantage of an nular slot antenna s over patch antennas is improved bandwidth. Conversely annular slot antennas generally radiate an omni directional pattern du e to the l ack of a ground plane whereas a directive antenna with good efficiency is preferred in biomedical app lications. A commonly used high efficiency directional antenna is a microstrip array but its large aperture size and narrow bandwidth at low GHz frequencies makes th is antenna undesirable for the current application and design frequency Therefore a prob e fed cavity antenna is chosen for this study because it is a highly efficient, broadband, directional radiator which can be scaled in size by introducing a dielectric fill.
52 4.3.1 CBSA Design Concept The CBSA consists of an annular slot antenna in contact with a cylindrical metal cavity  T he CBSA dimensions are given in Figure 29 The cavity is filled with a Teflon dielectric, and excited by a n internal coaxial probe. The internal probe excites the inner patch of the annular slot aperture. Frequency tuning of the antenna is another important feature of the internal probe, enabling detection at multiple sensing depths. Tunable antennas are es pecially useful in the biomedical arena for detection of multiple clinical diagnostic points. Implementation of the cavity further improves antenna bandwidth, gain, directivity, and suppresses surfaces curre nts while forcing radiation in broadside directi on towards the TUI The dielectric fill allows for reduced aperture size, and lower frequency operation. An adjustable specimen holder is integrated on top of the cavity which regulates the distance between the phantom and antenna from 7 mm 25 mm, the estimated distance between the body and projected health monitoring device.
53 Figure 29 Dimensions of the CBSA. 4.3.2 Simulations The CBSA was simulated in Ansoft HFSS to validate that the desired antenna characteristics were achieved. The material properties of the Plexiglas specimen holder and Teflon used to fill the cavity were not uniform and varied from sample to sample. As a r esult, the Plexiglas and Teflon were characterized using the Agilent HP8750 dielectric probe kit, and modeled in HFSS. The antenna was initially designed to operate in free space then redesigned for functionality in close proximity (7 mm) to a skin tissue phantom ( # r ~44). The skin phantom was also characterized in house and modeled in the simulator. As illustrated in Figure 30 the various antennas parameters provide design flexibility with regard to size, bandwidth and design frequency. The resonant frequency decreases for increased values of W , i, # r and o. Bandwidth increases for increased values of W, D, and t and decre ases as # r is increased. In general, the design process Symbol Dimension Size (mm ) W Width of Slot 10 i Inner Conductor Radius 21 o Outer Conductor Radius 45 L Feed Length 48 D Cavity Depth 27 D Teflon Fill Depth 25 W Width of Slot 10 Crossed Slots LxW 24x2 20x2 Short LxW 12.5 x 6 "#$%&'()*%% Feed Insert Point !"#$%"&'()$$* +( +&,-#. +/01( Dielectric Filled Cavity ,--.#/( 0'2#(1"#$""&()%2"# 01&..(2%&/ 0'2#(1"#$""&(/&34 23&1/ 0&'456/&1
54 involves configuring t hese parameters for optimal antenna performance at short distances from the TUI. Figure 30 CBSA design parameters and their effect on bandwidth (BW) and design frequency ( f c ). As illustrated in Figure 31 the simulation results prove that the CBSA is broadband (300 MHz), and works well in close proximity to a skin tis sue phantom at the design frequency of 1.4 GHz. Simulations also show that the antenna is very efficient (88%), and tunable to ~50 MHz per mm (MHz/mm) of the feed length ( Figure 31 ). The simulated gain and directivity are 3.4 and 3.9 dB, respectively. Parameter Variation Effect BW f c W Increase i Increase N/C o Increase N/C " r Increase " L Increase N/C D Increase t Increase Crossed Slots N/C t Substrate (Sub) Thickness Internal Feed L Teflon Fill D !"#$%& !'() (*+%,)-%.--",/0+-% w i o cross slot
55 Figure 31 Simulations if S11 in close proximity to a muscle tissue phantom. This figure also shows t unability as a function of feed L: 50 MHz/mm 4.3.3 Measurement s and Human Body Characterization The CBSA w as fabricated and measurements were performed in three conditions: i n close pro ximity to a skin tissue phantom, in free space and i n close proximity to a human core. Following are the details of the experiments in each condition. First the antenna is positioned in close proximity to a skin tissue phantom. T he measured and simulated results are comparable. The reflection coefficient s at the design frequency (1.4 GHz) are 22 dB and 20 dB for measurements and simulations, respectively. The measured b andwidth is ~400 MHz, which is ~100 MHz wider than that of the simulation ( Figure 32 ). The difference between the measurement and simulation is likely due to the difficulty in fabricating a cavity antenna without boundary disconti nuities between the cavity walls and radiating aperture (slot antenna). Previous research has shown that nearly perfect contact is needed between waveguide structures to -25 -20 -15 -10 -5 0 1 1.2 1.4 1.6 1.8 2 S11 (dB) Frequency (GHz) Feed L=48 Feed L=49 Feed L=50
56 avoid boundary condition discontinuities. Whereas the CBSA cavity is analogous to a cylindrical waveguide, any slight discontinuity in the waveguide/cavity walls can produce variations in the surface currents and thus impedance. Figure 32 S11: measured versus simulated results with the phantom offset 7 mm fr om the CBSA. Second the antenna is characterized while radiating in free space. The measurement results in Figure 33 confirm that directionality was achieved. The measured and simulated radiation pattern results were also comparable. The offset between the antenna and tissue is chosen at the distance in which the worst case degradation occurred in the preliminary stud y. By analyzing S11 data in Figure 13 it is apparent that the antenna degradation is inversely proportional to the offset distance, with 7 mm being the worst case scenario. Since an acceptable performance can be achieved at larg er offset distances, the an tenna is designed for optimal performance in the worst case scenario. Therefore the 7 mm offset was chosen for the remainder of this study. -25 -20 -15 -10 -5 0 1 1.2 1.4 1.6 1.8 2 S11 (dB) Frequency (GHz) Measurement Simulation
57 The measurement results in Figure 34 show that at 1.4 GHz the CBSA has a very high reflection when radiating in free space, but when positioned in close proximity to the phantom the reflection is very small, enabling the detection of very low emissions from the TUI with very low signal loss due to mismatch This feature could also be used to automatically activate the sensor when brought into a certain distance from the body. Figure 33 Measured versus simulated normalized radiation pattern of CBSA in dB scale -30 -20 -10 0 0 90 180 270 CBSA Meas Free Space CBSA Sim Free Space
58 Figure 34 S11 in free space versus phantom with 7 mm offset. Finally, the antenna was characterized 7 mm from the core of a human subject t o verify that the antenna performance holds in practice Figure 35 shows that the S11 of the antenna in close proximity to the phantom and core of the human subject are virtually identical. This data provides further evidence that the phantom as well as the antenna are well suited for pre clinical biomedical experimentation. -25 -20 -15 -10 -5 0 1 1.2 1.4 1.6 1.8 2 S11 (dB) Frequency (GHz) Phantom Free Space
59 Figure 35 S11: human core versus phantom with 7 mm offset. 4.4 Measurement Test Bed The measurement test bed is a three layer human core model (HCM) which mimics a conical volume of an abdominal cavity, 50 mm deep with diameters of 55 mm and 75 mm at d = 0 and d = 50 mm, respectively. As illustrated in Figure 36 this volume ideally captures the antenna sensor main probing region incident to the stomach which generally takes the form of a Gaussian contour. The HCM is comprised of layered volumes of the solid skin muscle tissue phantom and liquid blood fatty tissue phantom previously presented in section 3.5 The ability of the HCM to accurately emulate a human core is demonstrated in the comparison of the electrical properties (Z, # r ) of the skin, muscle, and blood fatty tissu e phantoms to the Gabriel model The results were strikingly comparable for each t issue layer; t he blood fatty tissue phantom comparisons are illustrated in Figure 18 Figure 19 the skin phantom in Figure 22 Figure 23 and the muscle phantom in Figure 24 Figure 25 -25 -20 -15 -10 -5 0 1 1.2 1.4 1.6 1.8 2 S11 (dB) Frequency (GHz) Phantom Core
60 4.4.1 Rationale for the Human Core Model The HCM was developed to provide a more concise electromagnetic model of an abdominal cavity than the more commonly used single layer phantoms Such phantoms are usually developed using simple solid, semi solid (gels), or liquid s olutions   P revious studies have proven that "dielectric layering greatly influences" t he r adiometric measurement, therefore single layer phantoms cannot accurately mimic the emissive properties of layered volumes human tissue  This loss in accuracy, could create considerable measurement errors, since microwave radiometers detect very low T B emissions which are dependent on the electrical properties of the tissue. L iquid phantoms usually comprised of saline or a water bolus have a dielectric constant similar to water (~78) at room temperature and 1.4 GHz, whereas human muscle has a dielectric constant of ~54, skin ~44, and fat ~10. As a result the detectable emissions from liquid phantoms will differ from those of human tissue. S emi solids or gel phantoms have been developed which have similar electri cal characteristics to that of skin and muscle tissue, however they are not as durable as solid phantoms. Though semisolids provide a more accurate representation of the body's electrical characteristics across the surface of the TUI some disadvantages e xist when modeling three dimensional volumes of the bo d y's clinical diagnostic regions. For instance thin tissue layers ( < 2 mm) such as skin are difficult to develop and manage. Moreover the versatility of the test bed is reduced, since less dense sem isolids may not hold the form factor of the tissue volume especially at elevated temperatures indicative to that of heat related disorders
61 Until this work, no solid skin muscle phantoms have been developed with electrical properties analogous to human tissue within the 1 2 GHz frequency band. There are some single layer phantoms (muscle) which employ an outer shell or cast to hold the form of the TUI However the electrical characteristics of the cast s usually plastic s are d istinctly dissimilar at the air skin interface This interface is the first and therefore critical boundary for extract ing subsurface data from the TUI due to sizable reflections which occur at that boundary which lead to radiometric signal loss.  presents a solid 2/3 rd muscle phantom which is the currently best available technology for mimicking a human torso Yet again this 33% difference in the dielectric constant may present significant measurement errors when extracting deep seated ti ssue temperatures using microwave radiometers 4.4.2 Design of t he Human Core Model The HCM is a durable phantom, designed to mimic the region of diagnosis for core body temperature monitoring, using a layered configuration of the phantoms previously presented in section 3.5 Layers 1 and 2 of the HCM make up the hybrid skin muscle phantom comprised of a composite material developed using water and TX 151 The skin layer has a non uniform thickness, ranging f rom 1 mm 2 mm, which is comparable to the combined thickness of the dermis, epidermis, and hypodermis. The muscle layer is located immediately below the skin layer, and also has a non uniform thickness of 7 mm to 8 mm. Core body temperature is essenti ally based on the temperature of the circulating blood through the cranial, thoracic and abdominal cavities  Therefore Layer 3, the inner core, is a liquid volume ~40 mm deep which mimics
62 blood and f atty tissue inside the stomach. The inner core is located inside of a plastic container which with housing to secure the skin muscle phantom approximately 1 mm in thickness Since the radiometer detects thermal emissions across the depth of the tissue, the effect of the contai ner is negligible being that it's a thin, highly emissive material, located beneath the critical air skin interface. Herein, e xtreme body temperature changes are simulated by varying th e temperature of the inner core to temperatures representative of hea t related disorders. Figure 36 The human core model (HCM). 4.5 Experimentation As illustrated in Figure 37 the measurement test bed is analogous to the experimental setup presented in the preliminary study, except the skin muscle phantom is added to complete the human core model (HCM). Although the second generation design incorporates various enhancements to the test bed the experimental procedure remained consistent with the 1 st generation design, to provide an exact performance 55 mm 50 mm Layer 1. Inner Core: Blood-Fatty Tissue Phantom Layer 2. Muscle Phantom Layer 3. Skin Phantom 8 mm 2 mm 40 mm
63 comparison and demonstrate the repeatability of the measurement. The measurements were performed with the HCM positioned approximately 7 mm from the antenna. In an effort to mimic changes in core body temperature; the temp erature of the skin and muscle phantom layers were kept constant, as the temperature of the core was varied just outside the dynamic range of extreme body temperatures; 107 ¡F 92 ¡F: Human body temperatures in the range of 92 ¡F to 100 ¡F are considered normal. Temperatures outside this range are considered adverse with T < 92 ¡F being hyperthermic, and T # 100 ¡F exhaustion or heat stroke  The physical temperature of the skin phantom was tracked using a thermocouple pla ced on the surface. The inner core was tracked using an average temperature from three evenly spaced internal thermocouples positioned at a depth of ~35 mm beneath the skin layer and ~22 mm beneath the muscle layer. The brightness temperature of the HCP was tracked using the radiometer and the raw data was processed via the NCM  The post processed NCM results are presented in section 5.2.1 along with a sensitivity analysis in the section 5.2.2
64 Figure 37 2 nd g eneration m easurement test bed. 4.6 Conclusion T his chapter presents the 2 nd generation design, which consists of a modified sensor design and enhanced antenna to circumvent obstructive phenomena which typically occur in the near field of the body. Device miniaturization and continuous ca libration allows for improved stability, accuracy, and resolution without the need for additional automatic gain control circuitry. The D C I/Q architecture enables device miniaturization by means of smaller components. In turn, thermal stability is ea sier to implement on devices with a smaller form factor. A multiport RF switch is added for continuous calibration which generates a calibration curve for each measurement interval. To facilitate optimal performance of the sensor at short distances from the TUI, a CBSA is designed to compensate for impedance mismatch, bandwidth degradation, and other near field effects previously demonstrated in the preliminary study. Table 8 demonstrates the antenna performance enhancements as compared to the 1 st generation design. These Data Logger Thermometer Inner Core: Blood/Fat Muscle CBSA T1 T2 T3 T4 8 mm 2 mm 40 mm Muscle Skin 25mm
65 performance specifications were selected are based on the antenna requirements for biomedical applications, presented in section 3.3 This chapter also presents an enhanced measurement test bed, which has been modified from a discrete to multi layer human core model (HCM) that mimics a three dimensional volume of an abdominal cavity The results from experimentation and testing o f the MRBS on t he HCM is presented in section 5.2.1 Table 8 PD1 versus CBSA performance characteristics. Parameter PD1 CBSA Resonant Frequency (GHz) 1.45 1.41 Gain (dB) 1.56 3.4 Directivity (dB) 2.45 3.9 Efficiency (unit less) 0.85 0.88 Near Field Bandwidth (MHz) 15 0 400
66 CHAPTER 5 THE NON CONTACT MODE L This chapter provides a comprehensive investigation to first identify then isolate the artifacts that obstruct the near field measurement. Although proper antenna design and offset distance can mitigate antenna body effects towards subsurface temperature tracking the preliminary study ( presented in section CHAPTER 3 ) as well as   provide evidence that simply minimizing near field effects is inadequate for ab solute temperature extraction This is mainly due to the fact that t he detectable energy emitted from deep seated tissue is yet quite difficult to extract due to various rea sons: 1) t hermal emissions at microwave frequencies are very low, on the order of 10 14 watts ; 2) t hese substantially faint signal levels are slightly larger than the ambient temperature noise floor and are extracted from a potentially noisy environment; 3) i n addition to 1) 2) t he detectable energy is attenuated considerably upon reaching the input of the receiver due certain artifacts which arise as a result of the non contacting nature of the sensor: I mperfections in the antenna design, and sizeable signal l oss at the air skin interface are the most critical. Therefore a Non Contact Model (NCM) is derived which correlates the observed brightness temperatur e to the subsurface temperature which accounts for 3), since the sensor itself is designed to compensate for 1) 2). Thereafter t he radiometric data extracted from experimentation in section 4.5 is processed through the NCM and a
67 sensitivity analysis is presented to determine the degree to which non contac ting artifacts effect and or degrade the measurement. 5.1 Derivation The Non Contact Model (NCM) presented herein provides a mathematical formulation to account for artifacts that arise from the sensor's remote positioning from the TUI. The parameters whi ch affect the measurement are first identified and then conjugated to derive the NCM. Though similar parameters have been presented in  from a far field remote sensing perspective, in this work the NCM parameters are define d in the context of near field radiometric sensing. Figure 38 illustrates the three stages of the NCM derivation presented in this section: 1) Measurement of Brightness Temperature, T'' SKN 2) Correction at the Antenna Interface, T' SKN 3) Correction at the Air TUI Interface, T SKN T SKN is the final output of the non contact model and represents the subsurface temperature across the depth, extracted at a point just below the surface of the skin.
68 Figure 38 Stages of the NCM. 5.1.1 Stage 1 Measurement of the Brightness Temperature Before applying the NCM, the specimen brightness temperature (T'' SKN ) is extracted from the measurement via calibration, which relates the input T'' SKN to the output indi cator (voltage, power, current), where T '' S YS is the total noise contribution delivered to the system before the NCM correction. In our case the voltage output is correlated to an absolute temperature from the physical temperatures of the calibration load s inside the radiometer. T ' SKN = T SYS ( 8 ) 5.1.2 Stage 2 Correction at the Antenna Interface The antenna is the primary sensing mechanism for non invasive extraction of biological data from the TUI, thus a complete understanding of the antenna parameters is of critical importance to obtaining an accurate measurement. Due to the close, non contact positioning of the sensor and the TUI, t he antenna parameters presented are characterized from a close proximity perspective. C B S A HCM MRBS T REV T P L(1-X)
69 The antenna efficiency ( % e ), physical temperature of the antenna (T p ) and the antenna transmission efficiency due to the impedance match (X), mutually affect the signal (biological data) detected by the antenna. An antenna with a low efficiency attenuates the detected signal by a factor of % e As discussed in Chapter 2 thermal conduction from the TUI heightens (T p ), in close proximity sensing applications. X is derived by first integrating the near field reflection coefficient ( A I ) across the antenna bandwidth B where ( f and df denote the f requency step of the integr al ( 9 ) Ideally the antenna is designed such that the 10 dB return loss bandwidth encompasses the frequency band of the radiometer as determined by its internal filtering. Transmission is denoted as one minus the reflection; ac cordingly the formula for X is presented in ( 9 ) X = 1 # A I B $ 2 df = 1 % f # A I 2 & B ( 9 ) The combination of suboptimal antenna efficiency and impedance mismatch attenuates the detected signal. Moreover, antenna TUI thermal conduction, results in the generation of thermal noise which propagates through the system and distorts the T'' SKN measur ement. These phenomena are modeled in ( 10 ) where T' SKN 1 is the first step in the T SKN derivation T SKN # 1 = T SYS # T p ( 1 # $ e ) X $ e X ( 10 ) From the antenna body near field the specimen brightness temperature is extracted via the main probing footprint, illustrated in Figure 39 which is equivalent to the antenna main lobe in the far field. This region also defines th e spatial resolution of the sensor. An antenna with a perfect broadside radiation is unrealizable. Therefore some ambient temperature contributions from the secondary probing hemisphere (T SL )
70 will affect the measurement. % ml and % sl represent the effici ency of the main probing footprint and secondary probing hemisphere, respectively. % ml is calculated through normalization of the antenna main beam efficiency resolved to its near field component, a similar approach is employed by near field ranges to res olve the far field radiation pattern; a review of the theory is presented in  The relationship between % ml and % sl is provided in ( 11 ) sl = 1 # ml ( 11 ) By combining equations ( 8 ) ( 11 ) the derivation incorporating all of the antenna parameters is presented in ( 12 ) where T' SKN 2 is the second step in the T SKN derivation T SKN # 2 = T SKN # 1 # T SL ( 1 # $ ml ) $ ml ( 12 ) As illustrated in Figure 38 noise emanating from the input of the radiometer receiver in the direction of the antenna ( T REV ) is a function of the transmission loss (L) in the signal path between the antenna and radiometer. T REV can be mitigated by integrating an isolator in the radiometer antenna transmission path. The noise temperature that is then reflected back into the system input is denoted by T' REV in ( 13 ) where T PI is the physical temperature of the component at the reflection interface (in this case an isolator termination). T REV = T pI L ( 1 # X ) ( 13 )
71 Figure 39 Antenna near field main primary probing footprint (90 " # 270) and secondary probing hemisphere (90 < < 270) in the elevation (" ) plane. The final derivation of the stage 2 NCM, incorporating the antenna interface correction and T' REV is presented in ( 14 ) and Figure 40 T SKN = T SKN # 2 # T REV = T SYS # T REV # T SL ( 1 # $ ml ) $ e X # T p ( 1 # $ e ) X $ e $ ml X ( 14 ) Figure 40 Corrections at the antenna interface. 0 45 90 135 180 225 270 315 CBSA Main Probing Footprint T SL C B S A MRBS T SKN 2 T SKN 1 T SL T REV T P L(1-X)
72 5.1.3 Stage 3 Correction at the Air TUI Interface Stage 3 of the NCM accounts for the effects of the specimen emissivity denoted by e The product of e with the physical temperature yields the specimen brightness t emperature. As described in  the input impedance of the antenna (50 ') is usually well matched to the human body (~59 ) at radio frequencies Thus, when the antenna is placed in direct body contact electromagnetic ( EM ) waves are coupled through the antenna body boundary with negligi ble interference. In non contact sensing applications EM propagation becomes non trivial due to impedance discontinuities across the air TUI boundary. H uman tissue typically has a very high relative permittivity # r with the lowest being fat ( # r = 9 ) an d the highest being blood ( # r = -59 ). When a material with a high dielectric constant is bounded by air, sizeable reflections are introduced. As a result weak EM emissions from the TUI are attenuated by a factor of 40% 60% at RF frequencies. This phen omenon significantly heightens the difficulty in attaining an absolute subsurface temperature measurement. Herein the emissivity of the TUI is represented by ( 15 ) and is related to the # r of the specimen by ( 16 ) The air skin reflection is defined by R A S with # r denoting the relative permittivity of the specimen. e = 1 R A S 2 ( 15 ) R A S = 1 # r 1 + # r ( 16 ) While the strong impedance mismatch at the air TUI interface attenuates the emissions from the TUI, it has the effect of intensifying the ambient atmospheric contributions
73 (T DN ). Accordingly, e R A S X, % ml and % e also impact the effect of T DN The comp lete NCM is presented in ( 17 ) T SKN = T SYS # T REV T SL ( 1 $ ml ) $ e X T p ( 1 $ e ) X T DN X $ ml $ e ( 1 e ) $ e $ ml Xe ( 17 ) 5.2 Implementation The NCM was app lied to radiometric data extracted from measurements performed on the enhanced test bed ( discussed in section 4.4 4.5 ) to emulate subsurface temporal monitoring. The accuracy of the NCM is validated first, through an analysis of the measurement data extracted from the test bed before and after being processed through the model. These results demonstrate a substantial improvement in accuracy after applying the NCM. Thereafter, a sensitivity analysis is performed to show the sensitivity of the measurement to the model parameters. 5.2.1 Data and Results In Figure 41 the extracted temperature profile of T SKN is compared with the physical temperatures of the skin and core. These results show that T SKN follows the thermal profile of the inner core, which is very different from the thermal profile of the skin surf ace. Also illustrated in Figure 41 is the degree to which the accuracy of the measurement is improved following application of each stage of the NCM. T'' SKN follows the thermal trend of the inner core more precisely than that of the skin layer but with minimal accuracy. As enhancements are added to the model, the correlation to the inner core temperature improves with T' SKN and T SKN provides the optimal response
74 Figure 42 shows the absolute percent difference between the physical temperature of the core and the extracted temperature s from each stage of the NCM. As the temperature of the core decreases as a function of time thermal energy is conducted through muscle and skin layers, which heightens the emissions from the intervening layers. In essence, the radiated emissions across the tissue depth are heightened at the T' SKN and T SKN interfaces. As a result the percent difference between the core, T' SKN and T SKN seem to decrease as a function of time as illustrated in Figure 42 The highest percent difference between T SKN and the core is 8 %, and this value will be considered as a reasonable percent difference threshold for the sensitivity an alysis that follows in section 5.2.2 The results in Figure 41 and Figure 42 also reveal that T SKN is lower than the physical temperature of the inner core. This result is expected and is due to the fact that wave propagation through the HCM layers is attenuated and non coherent, resulting i n reflections and signal loss from layer to layer. As a result the percent difference between the physical and radiometric measurements are fairly high. A direct correlation between the detected brightness temperature and the inner core temperature requi res the additional step of incorporating the propagation effects of the HCM into the extraction process, which is demonstrated in the chapter following
75 Figure 41 Physically measured temperatures of skin and core model (dashed lines) and brightness temperature measurements (solid lines) before (T'' SKN ) and after applying the NCM (T' SKN T SKN ). Figure 42 Absolute, p ercent difference between the core temperature (Nom), skin surface (Skin) and radiometer measurements before (T'' SKN ) and after ( T' SKN T SKN ) applying the NCM. 70 75 80 85 90 95 100 105 110 Termperature (F) Time T SKN T'' SKN T' SKN Skin Core Nom Skin T'' SKN T' SKN T SKN -5 0 5 10 15 20 25 30 Percent Error (PE) Time
76 5.2.2 Sensitivity Analysis of the NCM Parameters A sensitivity analysis was performed to determine the model parameters to which the measurement is most sensitive, which would in turn identify the parameters which require more precise characterization and monitoring. The nominal value of each parameter is assumed to provide the optimal T SKN response. The analysis is performed via percent error plots of T SKN as the NCM parameters are varied from their nominal values within ranges that would be realizable in practice. Certain parameters cause a change in the T SKN response over time therefore the analysis is performed in 15 minute intervals with "start" denoting the point in the me asurement at which the core temperature is 107 F. Figure 43 demonstrates that if X is slightly degraded to 0.9 from 0.9 57 the percent error would be 12 %, which is much greater than the 8 % threshold. This result is noteworthy because the characteristics of most antennas vary when in close proximity to biological media. In practice, X could degrade to well below 0.9. An accurate measurement was achieved in this work by designing the antenna for optimum functionality in close pr oximity to the TUI, therefore minimizing input match reflections. As shown in Figure 44 the measurement is also quite sensitive to T DN A 5% variation from the nominal T DN value of 65 F (ambient temperature), induces error perc entages of 3 6%, which is also well beyond the threshold. This is attributed to the fact that sizable contributions of T DN are reflected across the tissue into the sensor, contrary to on body radiometric sensors which have no reflected T DN contribution due to the sensor being in direct contact with the TUI. In practice T DN varies with the temperature of the space suit and therefore must be known to a high degree of accuracy. Implied by equation s ( 15 )
77 ( 17 ) this T DN reflection phenomenon has the greatest effect on media with a high dielectric constant such as skin tissue. Figure 43 Percent error in the T SKN measurement taken at 15 minute intervals as X is varied from t he nominal value (Nom) of 0.957 0 20 40 60 80 100 120 140 160 180 200 Nom-.957 0.95 0.9 0.8 Percent Error X Start / 15min / 30min
78 Figure 44 12 Percent error in the T SKN measurement taken at 15 minute intervals as T DN is varied from the nominal value (Nom) of 65 F. The measurement is least sensitive to T p e % e % ml and especially $ SL (see Figure 45 ) which further justifies the close proximity approach and enables design flexibility. For instance, section 2.1 references previous works which describe placement issues associated with the on body approach that distort the measurement such as thermal con duction between the specimen and $ P Figure 46 provides evidence that the close proximity measurement is not very sensitive to $ P However, this parameter should be known with good accuracy, since the percent error increases beyo nd the desired 8 % threshold as T P is varied by 5%. Figure 47 illustrates that the measurement is least sensitive to e and the percent error varies with respect to time. This data implies that variations in e from person to per son will have minimal effect on the accuracy of the close proximity measurement. The same analysis was performed on % e and % ml and the percent error results were virtually identical there was a small variation in T SKN -40 -20 0 20 40 60 80 5% Nom # 5% # 10% Percent Error T DN Start / 15min / 30min
79 measurement over time and the 8 % error thresholds occurred around 0.6, whereas the nominal values a re 0.88 and 0.95, respectively Figure 48 Figure 45 Percent error in the T SKN measurement taken at 15 minute intervals as T SL is varied from the nominal value (Nom) of 65 F -5 -3 -1 1 3 5 7 5% Nom # 5% # 10% Percent Error T SL Start / 15min / 30min
80 Figure 46 Percent error in the T SKN measurement taken at 15 minute intervals as $ P is varied from the nominal value (Nom) of 65 K Figure 47 Percent error in the T SKN measurement taken at 15 minute intervals as e is varied from the nominal value (Nom) of 0.444 -10 -5 0 5 10 15 20 5% Nom # 5% # 10% Percent Error T P Start / 15min / 30min -10 -8 -6 -4 -2 0 2 4 6 8 10 0.355 Nom-.444 0.533 0.622 Percent Error e Start / 15min / 30min
81 Figure 48 Percent error in the T SKN measurement taken at 15 minute intervals as % e is varied from the nominal value (Nom) of 0.88 5.3 Conclusion A mathematical representation in the form of a non contact model was derived and implemented on data extracted from close proximity measurements performed on the HCM. The correlation between th e physical temperature of the inner core of the human phantom and the extracted subsurface temperature was within 8% difference. In C HAPTER 6 further enhancements are achieved by implementing a model to account for propagation effects throughout the phantom. A sensitivity analysis was performed to determine which model parameters the measurement is most sensitive to. This work provides evidence that the measurement is most sensitive to atmospheric contributions and antenna im pedance match, the latter being influenced by the presence of biological media. The close proximity measurement is less sensitive to the physical temperature of the antenna, which has been known to distort on body measurements. Moreover minimal sensitivi ty to the antenna efficiency -50 -40 -30 -20 -10 0 Nom-0.88 0.9 0.7 0.4 Percent Error % e Start / 15min / 30min
82 and main probing hemisphere enables antenna design flexibility. The measurement is least sensitive to the emissivity of the specimen, which implies that the MRBS performance will have minimal variation from person to person.
83 CHAPTER 6 TISSUE PROPAGATION M ODEL (TPM) This chapter presents a mathematical model for in coherent propagation of thermal radiation through out the human body The model is developed to complement subsurface body temperature measurements made using the MRBS, and processed through the NCM. The data presented in this chapter was aggregated from the experiment in section 4.5 The NCM was applied to the experimental data and the results presented in section 5.2.1 In this chapter, t he post processed NCM data is yet again processed through the TPM, which further improves the accuracy towards a n abs olute core body temperature measurement The core body temperature extraction process is presented in section 6.4 6.1 Rationale for the TPM Microwave radiometers detect the brightness temperature of the specimen across the sensing depth, which is dependent on the electrical properties of the intervening tissue layers For this reason, previous studies have demonstrated that "dielectric layeri ng greatly influences" the radiometric measurement  In the context of electromagnetic wave propagation, the human body is characterized as a lossy medium, comprised of stratified tissue with dissimilar permittivity values. These characteristics heighten the complexity of extracting subsurface physiological data from the body. As electromagnetic waves propagate through the body a portion of the power is dissipated
84 due to the lossy nature of the tissue. Th e isotropically p ropagating energy is further attenuated by dielectric mismatch which gives rise to reflect ions at the tissue boundaries As a result thermal emissions radiated from deep within the body have only a marginal e ffect on the brightness temperature at the skin surface, making it very difficult to monitor changes in core body temperature without considering the electrical properties of the blood and muscle tissue Supporting data has been presented in physiological studies which provides evidence that the skin surface temperature alone does not provide an accurate estimate of core body temperature even with correction  In fact thermal variations on the order of 7 F from homeostasis 98 F, will only res ult in a change in skin temperature of 1 F. Here the need for a non invasive measurement method becomes apparent. In section 4.5 subsurface temperature variations of the HCM were tracked using the MRBS without considering a priori knowledge of the electrical properties of the internal tissue, i.e. muscle and blood fat. Only the dielectric properties of the skin surface were considered in the analysis. After applying the NCM, a n acceptable percent difference of 1.2% 8% w as achieved b etween the physical temperature measured internally using thermal probes and the radiometric brightness temperature even though the emissive properties of the deep seated tissue were not considered (see Figure 42 in section 5.2.1 ) Nevertheless, the accuracy of the measurement can be improved by taking the electromagnetic properties of the subcutaneous tissue into account. Moreover, the percent difference between the brightness temperatur e and physical temperature should be minimal, well below 3 ¡ F (3%), since small deviations in core body temperature are
85 used in the diagnos i s of heat related disorders  and as a pre clinical diagnostic tool for disease and other health related abnormalities. For instance, thermal homeostasis of the human body is maintained from 98 ¡ F to 100 F Heat exhaustion and stroke are diagnosed at temperatures above 104 ¡ F, which is only ~6% above homeostasis. Moderate to severe hypothermia is diagnosed below 90 F or 9% below homeostasis. Therefore the percent difference values achieved using only the NCM are unacceptable for true core body sensor. Hence, the goal of this work is to improve the accuracy of the close proximity radiometric sensing modality to a perce nt difference value well below 2 % by introducing a mathematical formulation to model radiative transfer through the human body. 6.2 The TPM Derivation The tissue propagation model (TPM) depicts radiative transfer thro ugh three tissue layers of an abdominal cavity compromised of skin, muscle, and blood fatty tissue Accordingly, the TPM derivation is applied to the HCM, with the tissue defined as stratified lossy dielectrics. Coherent transmission effects and angular d ependence is ignored in the TPM since scattering will be negligible at the air skin boundary which is spatially homogeneous, given that the wavelength of the sensing frequency of 1.4 GHz ( & = 230 mm ) is much larger than the roughness of the tissue under investigation TUI  keratinocyte skin cells with size and roughness on the order of micr ometers Therefore, in our case the more complicated coh erent approach, will yield results very similar to that of the incoherent appro ach, as demonstrated in the final analysis. It has also been proven that the angular dependence is negligible in media with a high dielectric constant 
86 such as human tissue, since the polarization of the waves emanating fro m the tissue will remain relatively normal to the respective boundary or transmission interface. Moreover, the radiated signal is expected to be co polarized with the observation angle of the sensor, assuming the device remains relatively parallel with th e TUI inside the uniform of servicemen. The TPM derivation is based on Ulaby's equations for apparent brightness temperature of a terrain with a nonuniform dielectric profile in  These equations have been correlated to the HCM, except the reflection at the muscle blood boundary is ignored since the dielectric contrast between muscle and blood fatty tissue layers is minimal. The TP M derivation is implemented in four levels: 1) Definition of the Individual S trata (tissue layer) E missions, T s .t 2) Derivation of the Up and Down W elling E missions per L ayer, T t.U and T t.D 3) Derivation of the N et Apparent E missions from all S tratum T B 4) Derivation of Apparent Brightness E missions, T AP.B A graphical representation of the TPM is presented below in Figure 49
87 Figure 49 Graphical representation of the TPM. 6.2.1 Definition of the Individual Strata E missions To begin the strata temperatures T s.t are defined which are the total transmitted emissions (before reflections) at each tissue layer, with t representing the tissue layer itself: t = a air t = sk skin t = ml muscle and t = bl blood The expressions for T s. t are provided in ( 18 ) ( 20 ) wherein L t is the loss in the tissue and T t is the physical temperature of the strata The formula for the loss contributions in each layer ( L t ), is presented in ( 21 ) where t is the attenuation constant ( 22 ) t is the thickness of the tissue layer, # r ,t '' is the imaginary part of the dielectric constant and # r ,t the real part, per layer. T s bl = T bl ( 18 ) T s ml = T ml 1 1 L ml # $ % & ( ( 19 ) T s sk = T sk 1 1 L sk # $ % & ( ( 20 ) Z ml Z sk Z bl BLOOD T ml L ml T bl T sk L sk MUSCLE SKIN AIR sk a ml T tD T Bt T tU Downward Emission Upward Emission Net: Emission
88 L t = e t # t ( 21 ) = # $ r t $ 0 2 1 + $ r t ' $ r t % & ( ) 2 % & ' ( ) * + 1 . / 0 1 1 ( 22 ) 6.2.2 Derivation of the Up and Down W elling Emissions per L ayer To derive an expression for the up and down welling contributions per layer, a similar procedure is followed to that of  wherein a binomial expansion (1 / ) 1 is formed from a derived expression which takes into account all reflections and losses throughout the stratified tissue. The formula for / is presented in ( 23 ) In this case, / accounts for losses and reflections between the air skin and muscle blood boundaries, while discarding the neg ligible reflection s at the skin muscle boundary. The closed form of the binomial series is multiplied by an additional (1 a ) to account for transmission at the air skin interface. We define this closed form expression as the coefficient of multiple reflections (CMR) in ( 24 ) where t is the reflection coefficient at the tissue boundary as illustrated in Figure 49 The CMR is used in the derivation of the individual up and or down welling temperature contributions in each layer. Thus, t he up welling contribution for the blood fatty tissue layer is presented in ( 25 ) while the up and dow n welling contributions for the muscle and skin strata are defined in ( 26 ) ( 27 ) and ( 28 ) ( 29 ) respectively.
89 = # ml # a L ml L sk ( ) 2 ( 23 ) CMR = 1 # a ( ) 1 # ml # a L ml L sk ( ) 2 ( 24 ) T bl U = T s bl 1 # ml L ml L sk $ % & ( ) CMR [ ] ( 25 ) T ml U = T s ml L sk # $ % & CMR [ ] ( 26 ) T ml D = T s ml ml L ml L sk # $ % & ( CMR [ ] ( 27 ) T sk U = T sk 1 1 L sk # $ % & ( CMR [ ] ( 28 ) T sk D = T s sk ml L ml 2 L sk # $ % & ( CMR [ ] ( 29 ) 6.2.3 Derivation of the Net Apparent Emissions from all S tratum The net apparent brig htness emissions from all stratum (T B ) is comprised of the up and or down welling emissions per layer, while taking all reflections into account. T he total up and down welling contributions for each individual layer is represented by T B.t in ( 30 ) ( 32 ) As illustrated in Figure 49 T B.bl acts as a source, due to its assumed infinite thickness, and only has an upwelling temperature contribution T bl. U ( 30 ) Infinite thickness is assumed in T B.bl since the depth of the blood fatty tissue layer goes beyond that of the sensor penetration depth. T B .ml and T B .sk are comprised of up welling emissions T t U as well as down welling emissions T t D These expression are provided in
90 ( 31 ) ( 32 ) Hence, T B is effectively the sum of t he net apparent emissions from all three layers ( 33 ) T B bl = T bl U ( 30 ) T B ml = T ml U + T ml D ( 31 ) T B sk = T sk U + T sk D ( 32 ) T B = T B bl + T B sk + T B ml ( 33 ) 6.2.4 Derivation of Apparent Brightness E missions The ultimate goal is to formulate an expression for the net apparent brightness temperature emitted at the skin surface T B.AP as a function of T Bt the emissi ons from the intervening layers. T AP.B takes into account the net brightness contributions from all stratum ( T B ( 33 ) ) as well as the down welling ambient temperature T DN As described in  T DN is attenuated by multiple reflections and losses in the tissue layers. By assuming, thermal equilibrium i.e. T sk = T ml = T DN T DN can be equated to T B to resolve a second coefficient of multiple reflections denoted by CMR2 ( 34 ) yielding ( 35 ) Thus the final expression for T B.AP is presented in ( 36 ) ( 34 ) ( 35 ) T B AP = T B + T DN ( 36 )
91 6.3 Applying the TPM By employing the formulas derived in section 6.2 the proces s of applying the TPM to the HCM is straightforward. T B.AP is a function of the reflections ( t ), electrical properties ( t L t ) and physical characteristics ( t T t ) of the strata where t is the attenuation constant, L t is the loss and t the thickness of layer t. The calculated values for t t t and L t are provided in Table 9 Illustrated in Figure 50 are the results from the comparison of the emitted brightness temperature calculated from T B.AP of the TPM in ( 36 ) to T' SKN the brightness temperature detected by the radiom eter. The coherent based Wilheit model is also used in the comparison to show that coherent propagation effects can indeed be ignored  This assumption is proved via the small percent between the TPM and Wilheit model ( Figure 51 ) The similarities in the curves demonstrate that the radiometric measurement T' SKN is analogous to that of the TPM (T B.AP ) and Wilhei t models with percent error values on the order of 1% 2.5%. Error values of this degree are quite impressive considering that the measurement is quite sensitive to many factors, as demonstrated in the analysis in section 5.2.1 For instance a 1 degree inaccuracy in the atmospheric temperature could yield error values on the order of 1 0% 15 % as illustrated in Figure 44 of section 5.2.2 Table 9 Calculated values of t Z t t and L t LAYER Z (mm) (unitless) (m 1 ) L (unitless) BLOOD 40 0 34.66 19.45 MUSCLE 8 0 .01 41.62 1.946 SKN 2 0.561 37.1 1.181
92 Figure 50 Emitted brightne ss temperature at the surface (S kin) of the HCP measured by the MRBS and compared to the TPM and Wilheit model. Figure 51 Percent error plots: MRBS TPM, MRBS Wi lheit, Model and Wilheit TPM 6.4 Core Body Temperature Extraction Ultimately core temperature extraction is plausible by solving for T bl in the T B.AP expression ( 37 ) t t t and L t are calculated from ( 21 ) ( 22 ) as a function of the 74 75 76 77 78 79 80 81 Surface Emissions (F) Time T' SKN MRBS Skin Wilheit T B.AP TPM -0.5 0 0.5 1 1.5 2 2.5 3 3.5 Percent Error (PE) Time MRBS TPM MRBS Wilheit TPM Wilheit
93 layer thicknesses t which in practice can be estimated based on the body fat percentage, weight, and height of the individual The remaining unknowns are T sk and T ml the physical temperatures of the skin, and muscle respectively T sk is typically a measurable quantity, monitored by an infrared thermometer. T ml is resolved by applying heat transfer theory to the tissue layers and deriving a differential equation to express the heat transfer profile of T ml as a function of T sk and T bl Finally, T' SKN can be substituted for the remaining unknown T B.AP since the two are analogous With all of the remaining unknowns resolved, core body temperature is extracted by solving sim ply for T bl in ( 37 ) T bl = L ml L sk 1 # ml $ % & ( ) T B AP T B sk T B ml T DN CMR $ % & ( ) ( 37 ) 6.5 Conclusion This chapter presents a derivation of the TPM which is the final component for core body temperature extraction using microwave radiometry The four level derivation is based on a similar procedure employed in  for net apparent brightness temperature of stratified dielectric media. The TPM is applied to the HCP and the results were compared to that of the radiometric measurem ent taken by the MRBS. The results were promising, yielding only marginal error on the order of 1.5% 2.5% Such promising results infer that the extraction of core temperature can be achieved with high accuracy by implementing mathematical models to su pplement the radiometric measurement, however certain parameters must be monitored to a high degree of accuracy.
94 CHAPTER 7 SUMM ARY AND RECOMMENDATIONS FOR FUTURE WORKS 7.1 Summary Presented is a microwave radiometer and associated design methods for non invasive monitoring of core body temperature. The long term goal is to develop a multifunctional radiometric health monitoring system deployable in side the uniforms of astronauts, with optimal functionality 2 cm 4 cm from the body Based on a review of the literature, we have identified certain drawbacks of the o n body approach which may be intolerable for the current application therefore a non contact modality is being investigated. This work demonstrates certain design c onsiderations for the close proximity approach however t he most significant contributions lie within the areas of antennas and propagation We begin with a preliminary study, in which certain occurrences which obstruct the close proximit y measurement ha ve been identified The antenna requirements for biomedical radiometric sensing were also presented. Based on these requirements, a half wavelength printed dipole (PD 1) was selected for 1 st generation sensor because it is a widely studied, compact, broad band aperture w ith a relatively simple design However, w hen brought in close proximity to the body the antenna characteristics are distorted in the form of resonance shifts, impedance mismatch and bandwidth degradation. These phenomena induce considerable degradation in the end to end system performance.
95 T hese obstructive artifacts are demonstrated empirically by characterizing the antenna in the near field of RF tissue phantoms which have been developed as the experimental test bed for measu rement and testing purposes. Compared to traditional saline phantoms, the test bed in this study is comprised of tissue phantoms with electrical properties closer to that of human tissue enabling more precise characterization of the antenna body effects a s related to sensor performance Solutions in the area of antenna design are provided by implementing an absorbing cavity to suppress unwanted radiation opposite the specimen. However the antenna characteristics change when inside the cavity; therefore t he antenna is reconfigured for cavity operation using common design techniques (impedance matching, frequency tuning). We have also discovered receiver instability issues which are represented by the variations in the slope of the calibration curves/equat ions, which is likely due to thermal drifts in the RF components. Based on findings from the preliminary study, a 2nd generation design was developed which incorporates continuous calibration for receiver instabilities an enhanced antenna design, and a ssociated non contact propagation model to correct for errors which arise due to the non contact ing nature of the sensor. The 2 nd generation sensor is 33% smaller than the 1 st generation design which in turn improves the stability and resolution of the system. The 2 nd generation antenna is a cavity backed slot antenna (CBSA) designed for non contact biomedical radiometric sending. Compared to the 1 st generation printed dipole antenna ( PD1 ) the CBSA is more efficient and provides a consid erable improvement in bandwidth ( B > + 150 ) MHz. The gain and directivity were also enhanced by at least 1.5 dB. By optimizing the antenna design parameters, the CBSA has been configured to meet the requirement s for biomedical applications and
96 account for near field antenna body effects. The antenna is broadband ( > 400 MHz) and very efficient (88%) enabling high sensor resolution. It is also a directional radiator designed at 1.4 GHz for targeted detectio n of core body temperature emissions from depths of < 27 mm. The internal feed enables tunability of 50 MHz/mm of the feed length and adds novelty to the design in biomedical applications by reducing the intensity of antenna feed currents which may interact with the body. Measurements and simulations of the antenna S11 in close proximity to the phantom are comparable, as well as the radiation pattern s From these results it was concluded that the CBSA is a good candidate for biomedical sensing applications and best suited for the current application relative to the PD1. Although the CBSA enhances end to end performance of the system, a perfect antenna is not realizable, therefore a mathematical representation in the form of a non contact mod el (NCM) was implemented to mitigate certain artifacts not accounted for in the antenna design The model is presented in three phases for extraction of the measurement, corrections at the antenna interface and a final correction at the critical air ti ssue boundary. Close proximity measurements were performed on the enhanced measurement test bed using the 2 nd generation sensor and the results were processed at each stage of the NCM The 2 nd generation sensor is a microwave radiometer designed for biomedical sensing applications ( MRBS ) The enhanced test bed is a three layer human core model (HCM) which mimics the dielectric properties of a human stomach volume; skin, muscle, and blood fatty tissue. As the blood temperature was varied within the range of normal body temperature and conditions of heat related disorders, the MRBS monitored the
97 brightness temperature of the HCM, while the physical temperatures were tracked using thermal probes positioned throughout the HCM. The measurement data was processed through the NCM and a sensitivity analysis was performed to determine which model parameters the measurement is most sensitive to. The results demonstrate that the measurement is most sens itive to atmospheric contributions and antenna impedance match, the latter being influenced by the presence of biological media. The close proximity measurement is less sensitive to the physical temperature of the antenna, which has been known to distort on body measurements. F urthermore minimal sensitivity to the antenna efficiency and main probing hemisphere enables antenna design flexibility. The measurement is least sensitive to the emissivity of the specimen, which implies that the MRBS performance will have negligible variation from person to person. It is important to note that proper shielding of the antenna and sensor fr om ambient noise is critical for achieving a highly accurate measurement. Ultimately, t he correlation between the core temper ature of the HCM and the extracted subsurface temperature was within 8 % difference after applying the NCM. With the goal of achieving a percent error of < 3%, t he accuracy of the measurement is further enhanced by developing a tissue propagation model (TPM) to account for losses and multiple reflections throughout the stratified tissue The TPM is based on Ulaby's derivation of an expression for the net emissions from a multilayer medium with a non uniform dielectric profile. Incoherency is assumed s ince propagation will be solely based on the power density of the propagating emissions, whereby phase effects are negligible. This assumption is mainly attributed to the fact that scattering will be minimal due to the size of skin cells as compared to the sensing wavelength. In
98 addition, the sensor is expected to remain relatively parallel with the tissue, which further negates phase and or angular dependence. The TPM derivation is presented in four levels beginning with a definition of the fundam ental model components and c omplexity is added at each level, towards the complete derivation. First the emissions from the individual strata (T s .t ) are defined at level 1 with t representing the tissue layer; sk = skin, ml = muscle and bl = blood fatt y tissue Next, the derivation of the up and down welling emissions per layer, T t.U and T t.D are presented in level 2 which are combined a t level 3, to make up the net apparent emissions from all strata (T B ). The atmospheric contributions (T DN ) are introduced at level 4 to complete the full derivation of the apparent brightness emission T AP.B radiated at the skin surface. Justification for the incoherent approach is demonstrated by comparing the TPM to the coherent Wilheit model, yielding percent er ror (PE) results of < .5%. Thereafter the TPM response is correlated to the brightness temperature measurement of the HCM from the MRBS. The percent error b etween the two measurements was < 3%. As a result the MRBS measurement can be substituted for th e output of the TPM, which provides an expression for the brightness temperature emissions measured at the skin surface, as a function of the subsurface tissue. Ultimately, this expression is used to extract core body temperature by sol ving for the remain ing unknowns: 1) The loss ( L t ), reflections ( t ), and attenuation ( t ) per layer (t) and are calculated b ased on the material properties; 2) the physical temperature of the skin ( T sk ) is a measurable quantity which is typically monitored using an infrared thermometer; 3) the physical temperature of the muscle layer ( T ml ) can be resolved using heat transfer theory by applying a system of differential equations at the tissue
99 boundaries ; 4) at this point the remaining unknowns have been resolved and the inner core temperature T bl can be extracted via first order linear equation. 7.2 Recommendations for Future Works To achieve the long term goal of developing a real time, field deployable radiometric health monitoring system we plan to continue this research with strong emphasis on optimizing the performance of the sensor, characterization of the antenna body near field, and refining of the cur rent tissue propagation model. The technical objectives are to: I) d esign a 3 rd generation sensor with en hanced gain control, data processing techniques and the capability of measuring changes in the emissivity of the specimen as well as temperature ; II ) perform an experimental study on the antenna body effects using various near field antennas to derive a model which characterizes the close proximity electromagnetic effects as a function of antenna offset di stance ; and III) refine the previously developed tissue propagation model to account for an additional tissue layer and perform a sensitivity analysis of the model parameters to determine the sensitivity of the measurement to different body types. The rationale for the enhancements to the 3 rd generation sensor are to measure the emissivity of the tissue, which changes as a function of temperature, and implement advanced design enhancements and averaging schemes Correcting for emissivity error which result s from temperature changes in the stratified tissue, is critical f or optimal accuracy in non contact as well as on body radiometric sensor technologi es  This correction is trivial at the skin surface, however the level of difficulty is heightened as a function of the tissue depth. Therefore an additional Dicke "emissivity" standard will be
100 added to the third generation design. The concept is to monitor variations in the emissivity of the standard by changing it s input mach until the radiometer is balanced, i.e. output = 0. This provides the emissivity profile of the tissue across the sensing depth. By adding the addi tional standard, there exists some degradation in resolution  To offset this loss in performance, a n additional automatic gain control stage will be implemented, which is expected to improve the accuracy of the sensor beyond our current percent error value of < 3% (see section 6.3 ) Ad ditional data processing techniques will also be implemented since t he calibration cycle of the current 2 nd generation design is approximately 1.4 s per measurement whereas the system is capable of thousands of calibration cycles per second. Improving th e frequency of calibration provides more measurement (data) samples which can be averaged using advanced algorithms to improve the resolution of the sensor. In an effort to better understand the antenna performance, as a function of the distance from th e body, we plan to characterize the antenna body near field by resolving constants to fit a near field propagation model. The design and development of directional antennas with optimal performance (S11 < 0 20dB, efficiency > .85) at short distances from the body is vital for the success of this project. In general, t he characteristics of various near field antennas will be measured at various distances from the human core tissue phantom model to complete stage 3 of a two por t network, whereas stage 1 is the electrical characteristics of the phantom model presented in section 3.5 and stage 2 is the antenna body near field which is considered as the device under test (DUT) Genetic algorithms will be used to match the DUT to the electrical response of stage 3. Repeatability across the various antenna types will enable the extraction of the electrical
101 constants to derive the near fi el d propagation model. This model will be used to design candidate antennas with characteristics that fit the model. The near field model will also enable the design of feedback networks with automatic impedance matching integrated onto the candidate antennas. Proposed are conformal geometries such as fabric antennas tha t can be easily integrated into uniforms or miniaturized cavity antennas in which the sensor can be fully integrated as a hand held device To further improve the accuracy of the current TPM, we plan to add an additional layer which can be used to model, fatty and connective tissue such as cartilage. The derivation will follow a similar procedure to that of section 6.2 Thereafter a sensitivity analysis will be performed to determine the sensitivity of the measurement to diff erent body types by changing the thickness and dielectric properties of the ti ssue within reasonable ranges f o r the human body. The exact values will be determined from a statistical analysis of data aggregated from an additional study which will be conducted to determine the thickness of the tissue layers of an abdominal cavity based on the height, weight, and age of the individual. The objective is to use the TPM to derive body standards for the sensor which can be generated by inputting the height weight, and age of each user. In essence, t his body type calibration customizes the sensor's measurement extraction algorithms for each individual user.
102 LIST OF REFERENCES  W.J. Y ang, S. Mochizuki, and P.T. Yang, "Applications of Microwave Radiation in Medicine," J ournal of Mech anics in Med icine and Biol ogy v ol 2, pp 53 63, Oct ober 2002  F. Sterzer, "Microwave medical devices," IEEE Microwave Magazine vol. 3, pp. 65 70, March 2002  A. Rosen, M.A. Stuchly, and A. Vander Vorst, "Applications of RF/microwaves in medicine," IEEE Transactions on Microwave Theory and Techniques vol. 50, pp. 963 974, March 2002  E. C. Fear S. C. Hagness, P. M. Meaney M. Okoniewski, and M. A. Stuchly "En hancing breast tumor detection with near field imaging," IEEE Microwave Magazine v ol 3, pp. 48 56, January 2002  L.M. Burdina I.G. Pinkhosevich V.A. Khailenko S.G. Vesnin and N.N. Tikhomirova "X Ray Diagnostics and X Ray Therapy in Clinic of XXI III Russian Scientific Forum pp. 49 50 2002  F Bardati and S. Iudicello, "Modeling the Visibility of Breast Malign ancy by a Microwave Radiometer, IEEE Transactions on Biomedical Engineering v ol 55, pp. 214 221, January 2008.  L.R. Ballew, "A Microwave Radiometer for use in Biomedical Sensing Applications Master's Thesis, Baylor University, 2006  O. Jay, F.D. Reardon, P. Webb, M.B. Ducharme, T. Ramsa, L. Nettlefold, and G.P. Kenny, "Estimating changes in mean body temperature for humans duri ng exercise using core and skin temperatures is inaccurate even with a correction factor Journal of Applied Physics vol., pp. 443 451, 2007  E. C. Green, "Design of a microwave sensor for non invasive determination of blood glucos e concentration," Mas ter's Thesis, Baylor University 2005.
103  A.T. Oikonomou, I.S. Karansiou, and N.K. Uzunogu, "Conformal Patch antenna for human brain imaging using near field radiometry, 5 th European Symposium on Biomedical Engineering, 2006  S. Jacobsen, and P. Stauffer, "Performance Evaluation of Various Antenna Configurations for Microwave Thermography During Superficial Hyperthermia Journal of Electromagnetism Waves and Applications, v ol 15, no 1, pp. 111 134, 2001  I.S. Karanasiou, A.T. Oikonomou and N.K.U zunoglu "Potential brain imaging using near field radiometry 4 th International Conference on Imaging Technologies in Biomedical Sciences September 2007  I.S. Karanasiou, K.T. Karathanas is, A. Garetsos A and N.K. Uzunoglu "Development and laborato ry testing of a noninvasive intracranial focused hyperthermia system IEEE Transactions on Microwave Theory and Techniques v ol 56, pp. 2160 2171, September 2008  K.L. Carr, "Antenna: the critical element is successful medical technology," IEEE MTT S International Microwave Symposium Digest v ol 1, pp. 525 527, May 1990  P. Racette, and R. H. Lang, "Radiometer design analysis based upon measurement uncertainty ," Radio Sci ence v ol 40, 2005 RS5004, doi:10.1029/2004RS003132  K. J.C. Tien, J. Judge, an d R.D. de Roo, Comparsion of different microwave radiometric calibration techniques," IEEE IGARSS v ol 6, pp 3748 3751, 2004  K.D. Stephan and J.A. Pearce, "Antennas and reflect ors for near field radiometric remote sensing of tempera ture in industrial applications, IEEE Antennas and Propagation Society International Symposium v ol 4, pp. 302 305, August 2002  F.L. Ulaby, R.K. Moore, and A.K. Fung, Microwave Remote Sensing, Active and Passive, v ol 1 pp. 354 356, Artech House Inc 1981  S. Jacobsen, and P. Stauffer, "Performance Evaluation of Various Antenna Configurations for Microwave Thermography During Superficial Hyperthermia Journal of Electromagnetism Waves and Applications v ol 15, no 1, pp. 111 134, 2001  W.J. Yang, S. Mochizuki and P .T. Yang "Applications of Microwave Radiation in Medicine," Journal of Mech anics in Med icine and Biol ogy v ol 2, pp 53 63, Oct ober 2002  T.L. Chen, "Printed Circuit Board Dipole Ant ennas and Dipole Antenna Array Operating at 1.8GHz," B.S. Thesis, Universi ty of Cape Town, 2003
104  Q. Bonds, T. Weller, B. Roeder and P. Herzig, "A tunable Cavity Backed Slot Antenna (CBSA) for close proximity b iomedical sensing applications," IEEE Microwaves, Communications, Antennas and Electronics Systems 2009  C. Gabriel, and S. Gabriel, "Compilation of the Dielectric Properties of Body Tissues at RF and Microwave Frequencies," Brooks AFB report number AL/OE TR 1996 0037 1996  Australian Communication Authority, "Radiocommunications (Electromagnetic Radiation Human Exposu re) Standard 2003," Radio Communications Act, 1992 Section 162, June 2003  American Sports Education Program (ASEP) "Heat Related Disorders ," 2001 http://www.khsaa.org/sports medicine/heat/hkheatrelateddisorders.pdf  G. Breed, "Design Issues for Direct Conversion Wireless Radios ," High Frequency Electronics, v ol 2, no 6, pp 48 51, June 2004  N. V. Larsen, and O. Breinbjerg, An L Band, Circularl y Polarized Dual Feed, Cavity Backed Annular Slot Antenna for Phased Array Applications," Microwave and Technology Letters v ol 48, pp. 873 878, May 2006  T Yilmaz T Karacolak, and E Topsakal, "Characterization of Skin Mimicking Gels for Implantable Antennas Operating at I SM Band (2.4 GHz 2.48 GHz) ," National Radio Science Meeting URSI 2008  K. Ito, "Numerical and Experimental Human Body Phantoms IEEE IET Seminar on Antennas and Propagation for Body Centric Wireless Communications 2007  M.S. Hawley, J. Conway, A.P. Anderson, and P.A. Cudd, "The influence of tissue layering on microwave thermographic measurements Int ernational Journal of Hyperthermia v ol 4, no 4, pp. 427 435, July 1988  C. L. Lim, C. Bryn, and J.K.W. Lee, "Human thermoregulation and measuremen t of body temperature in exercise a nd clinical settings, Annals Academy of Medicine v ol 4, pp 347 353, April 2008  Q. Bonds, J. Gerig, T. Weller, and B. Roeder, "Towards Core Body Temperature Measurement via Close Proximity Radiometric Sensing ," IEEE Sensors Journal, Special Issue on Non Invasive Physiological Monitoring, submitted August 2010  F.L. Ulaby, R.K. Moore, and A.K. Fung, Microwave Remote Sensing, Active and Passive, v ol 1., pp. 204 210 Artech House Inc 1981
105  J.D. Jackson, "How the antenna launches its power into radiation: The pattern of the Poynting vector at and near the antenna The American Journal of Physics, v ol 74, pp. 280 288, April 2006  Q. Bonds, T. Weller, B. Roeder and P. Herzig, "A Total Power Radiometer (TPR) and Measurement Test Bed for Non Contact B iomedical Sensing Applications," IEEE Wireless and Microwave Technology Conference, 2009  F.L. Ulaby, R.K. Moore, and A.K. Fung, Microwave Remote Sensing, Active and Passive, v ol 1. pp. 236 2 44, Artech House, 1981  T. T. Wilheit, "Radiative transfer in a plane stratified dielectric," IEEE Transactions on Geoscience and Remote Sensing v ol 16, pp. 138 143, 1978  F. Sterzer Temperature measuring microwave radiometer apparatus U.S. Patent 5949845 September 1999  N. Skou and D. L. Vine, Microwave Radiometer Systems Design and Analysis second edition, Artech House Inc, 2006.